Polyphase Decomposition
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Transcript of Polyphase Decomposition
1
PolyphasePolyphase DecompositionDecompositionThe DecompositionThe Decomposition
• Consider an arbitrary sequence{ x[n]} with a z-transformX(z) given by
• We can rewriteX(z) as
where
∑∞−∞=
−= nnznxzX ][)(
∑ −=
−= 10
Mk
Mk
k zXzzX )()(
∑∑ ∞−∞=
−∞−∞=
− +== nn
nn
kk zkMnxznxzX ][][)(
10 −≤≤ Mk
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PolyphasePolyphase DecompositionDecomposition
• The subsequences are called the polyphasepolyphase componentscomponents of the parent sequence{ x[n]}
• The functions , given by the z-transforms of , are called thepolyphasepolyphase componentscomponents of X(z)
]}[{ nxk
]}[{ nxk
)(zX k
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PolyphasePolyphase DecompositionDecomposition• The relation between the subsequences
and the original sequence { x[n]} are given by
• In matrix form we can write
]}[{ nxk
10 −≤≤+= MkkMnxnxk ],[][
[ ]
=
−
−−−
)(
)(
)(
....)( )(
MM
M
M
M
zX
zX
zX
zzzX
1
1
0
111 ....
4
PolyphasePolyphase DecompositionDecomposition
• A multirate structural interpretation of the polyphase decomposition is given below
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PolyphasePolyphase DecompositionDecomposition
• The polyphasepolyphase decomposition of an FIR decomposition of an FIR transfer functiontransfer function can be carried out by inspection
• For example, consider a length-9 FIR transfer function:
∑=
−=8
0n
nznhzH ][)(
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PolyphasePolyphase DecompositionDecomposition• Its 4-branch polyphase decomposition is
given by
where
)()()()()( 43
342
241
140 zEzzEzzEzzEzH −−− +++=
210 840 −− ++= zhzhhzE ][][][)(
11 51 −+= zhhzE ][][)(
12 62 −+= zhhzE ][][)(
13 73 −+= zhhzE ][][)(
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PolyphasePolyphase DecompositionDecomposition• The polyphasepolyphase decomposition of an IIR decomposition of an IIR
transfer functiontransfer function H(z) = P(z)/D(z) is not that straight forward
• One way to arrive at an M-branch polyphasedecomposition of H(z) is to express it in the form by multiplying P(z) and D(z) with an appropriately chosen polynomial and then apply an M-branch polyphase decomposition to
)('/)(' MzDzP
)(' zP
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PolyphasePolyphase DecompositionDecomposition•• ExampleExample - Consider
• To obtain a 2-band polyphase decomposition we rewriteH(z) as
• Therefore,
where
1
1
31
21−
−
+−=
z
zzH )(
2
1
2
2
2
21
11
11
91
5
91
61
91651
)31)(31(
)31)(21()( −
−
−
−
−
−−
−−
−−
−−
−+
−+−
−+−− +===
z
z
z
z
z
zz
zz
zzzH
)()()( 21
120 zEzzEzH −+=
11
1
91
5191
610 −−
−
−−
−+ ==
zz
z zEzE )(,)(
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PolyphasePolyphase DecompositionDecomposition
• Note:The above approach increases the overall order and complexity ofH(z)
• However, when used in certain multiratestructures, the approach may result in a more computationally efficient structure
• An alternative more attractive approach is discussed in the following example
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PolyphasePolyphase DecompositionDecomposition•• ExampleExample - Consider the transfer function of
a 5-th order Butterworth lowpass filter witha 3-dB cutoff frequency at0.5π:
• It is easy to show thatH(z) can be expressed as
1 5
2 4
0.0527864 (1 )
1 0.633436854 0.0557281( ) z
z zH z
−
− −+
+ +=
+
= −
−
−
−
++−
++
2
2
2
2
5278601
5278601
10557301
105573021
z
z
z
z zzH.
.
.
.)(
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PolyphasePolyphase DecompositionDecomposition
• Therefore H(z) can be expressed as
where
= −
−
++
1
1
5278601
52786021
1 z
zzE.
.)(
= −
−
++
1
1
10557301
105573021
0 z
zzE.
.)(
)()()( 21
120 zEzzEzH −+=
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PolyphasePolyphase DecompositionDecomposition
• Note: In the above polyphase decomposition, branch transfer functions are stable stable allpassallpass functionsfunctions
• Moreover, the decomposition has not increased the order of the overall transfer function H(z)
)(zEi
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FIR Filter Structures Based on FIR Filter Structures Based on PolyphasePolyphase DecompositionDecomposition
• We shall demonstrate later that a parallel realization of an FIR transfer functionH(z) based on the polyphase decomposition can often result in computationally efficient multirate structures
• Consider theM-branch Type I Type I polyphasepolyphasedecompositiondecomposition of H(z):
)()( 10
Mk
Mk
k zEzzH ∑ −=
−=
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FIR Filter Structures Based on FIR Filter Structures Based on PolyphasePolyphase DecompositionDecomposition
• A direct realization ofH(z) based on the Type I Type I polyphasepolyphase decompositiondecomposition is shown below
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FIR Filter Structures Based on FIR Filter Structures Based on PolyphasePolyphase DecompositionDecomposition
• The transposeof the Type I polyphase FIR filter structure is indicated below
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FIR Filter Structures Based on FIR Filter Structures Based on PolyphasePolyphase DecompositionDecomposition
• An alternative representation of the transpose structure shown on the previous slide is obtained using the notation
• Substituting the above notation in the Type I polyphase decomposition we arrive at theType II Type II polyphasepolyphase decompositiondecomposition:
)()( 10
)1( MM M zRzzH ll
l∑ −=
−−−=
10),()( 1 −≤≤= −− MzEzR MM
Mlll
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FIR Filter Structures Based on FIR Filter Structures Based on PolyphasePolyphase DecompositionDecomposition
• A direct realization ofH(z) based on the Type II Type II polyphasepolyphase decompositiondecomposition is shown below
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Computationally Efficient Computationally Efficient DecimatorsDecimators
• Consider first the single-stage factor-of-Mdecimator structure shown below
• We realize the lowpass filterH(z) using the Type I polyphase structure as shown on the next slide
M][nx )(zH ][nyv[n]
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Computationally Efficient Computationally Efficient DecimatorsDecimators
• Using the cascade equivalence #1cascade equivalence #1 we arrive at the computationally efficient decimator structure shown below on the right
Decimator structure based on Type I polyphase decomposition
y[n] y[n]x[n]x[n]
][nv
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Computationally Efficient Computationally Efficient DecimatorsDecimators
• To illustrate the computational efficiency of the modified decimator structure, assumeH(z) to be a length-N structure and the input sampling period to beT = 1
• Now the decimator outputy[n] in the original structure is obtained by down-sampling the filter outputv[n] by a factor ofM
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Computationally Efficient Computationally Efficient DecimatorsDecimators
• It is thus necessary to computev[n] at
• Computational requirements are thereforeNmultiplications and additions per output sample being computed
• However, asn increases, stored signals in the delay registers change
...,2,,0,,2,... MMMMn −−=
)1( −N
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Computationally Efficient Computationally Efficient DecimatorsDecimators
• Hence, all computations need to be completed in one sampling period, and for the following sampling periods the arithmetic units remain idle
• The modified decimator structure also requiresN multiplications and additions per output sample being computed
)1( −N
)1( −M
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Computationally Efficient Computationally Efficient Decimators and InterpolatorsDecimators and Interpolators
• However, here the arithmetic units are operative at all instants of the output sampling period which isM times that of the input sampling period
• Similar savings are also obtained in the case of the interpolator structure developed using the polyphase decomposition
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Computationally Efficient Computationally Efficient InterpolatorsInterpolators
• Figures below show the computationally efficient interpolator structures
Interpolator based on Type I polyphase decomposition
Interpolator based on Type II polyphase decomposition
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Computationally Efficient Computationally Efficient Decimators and InterpolatorsDecimators and Interpolators
• More efficient interpolator and decimator structures can be realized by exploiting the symmetry of filter coefficients in the case of linear-phase filtersH(z)
• Consider for example the realization of afactor-of-3(M = 3) decimator using alength-12 Type 1linear-phase FIR lowpassfilter
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Computationally Efficient Computationally Efficient Decimators and InterpolatorsDecimators and Interpolators
• The corresponding transfer function is
• A conventional polyphase decomposition ofH(z) yields the following subfilters:
54321 ]5[]4[]3[]2[]1[]0[)( −−−−− +++++= zhzhzhzhzhhzH
11109876 ]0[]1[]2[]3[]4[]5[ −−−−−− ++++++ zhzhzhzhzhzh
3210 ]2[]5[]3[]0[)( −−− +++= zhzhzhhzE
3211 ]1[]4[]4[]1[)( −−− +++= zhzhzhhzE
3212 ]0[]3[]5[]2[)( −−− +++= zhzhzhhzE
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Computationally Efficient Computationally Efficient Decimators and InterpolatorsDecimators and Interpolators
• Note that still has a symmetric impulse response, whereas is the mirror image of
• These relations can be made use of in developing a computationally efficient realization using only6 multipliers and11 two-input adders as shown on the next slide
)(1 zE)(0 zE
)(2 zE
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Computationally Efficient Computationally Efficient Decimators and InterpolatorsDecimators and Interpolators
• Factor-of-3decimator with a linear-phase decimation filter
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A Useful IdentityA Useful Identity• The cascade multirate structure shown
below appears in a number of applications
• Equivalent time-invariant digital filter obtained by expressingH(z) in its L-term Type Ipolyphase form is shown below
L LH(z)x[n] y[n]
)(10
Lk
Lk
k zEz∑ −=
−
x[n] y[n])(0 zE