Methods for measuring RF radiation properties of small antennas
Prof. D. R. Wilton Notes 22 Antennas and Radiation Antennas and Radiation ECE 3317 [Chapter 7]
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Transcript of Prof. D. R. Wilton Notes 22 Antennas and Radiation Antennas and Radiation ECE 3317 [Chapter 7]
Prof. D. R. Wilton
Notes 22Notes 22
Antennas and Radiation Antennas and Radiation
ECE 3317
[Chapter 7]
Antenna Radiation
Antenna Radiation
We consider here the radiation from an arbitrary antenna.
The far-field radiation acts like a plane wave going in the radial direction.
+-
x
y
z
r
, ,r r
r "far field"
S
Antenna Radiation (cont.)
The far-field has the following form: ˆ ˆE E E
ˆ ˆH H H
0
E
H
0
E
H
x
y
z
E
HS
x
y
z
HE
S
Antenna Radiation (cont.)
The far-field Poynting vector is now calculated:
*
* *
* *
0 0
22
0 0
1S E H
21 ˆ ˆ ˆ ˆE E H H21
ˆ E H E H2
EE1ˆ E + E
2
EE1ˆ
2
r
r
r
0
E
H
0
E
H
Antenna Radiation (cont.)
Hence we have
22
0
1ˆS E E
2r
2
0
EˆS
2r
or
Note: in the far field, the Poynting vector is purely real (no reactive power flow).
Radiation Pattern
The far field always has the following form:
0
E , , E ,jk r
Fer
r
E ,F Normalized ar electric fieldf
In dB:
10
E ,dB , 20log
E ,
F
Fm m
,m m direction of maximum radiation
Radiation Pattern (cont.)The far-field pattern is usually shown vs. the angle (for a fixed angle ) in polar coordinates.
10
E ,dB , 20log
E ,
F
Fm m
0 dB
30°30°
60°
120°
150° 150°
120°
60°
m
0
-10 dB
-20 dB
-30 dB
Radiated Power
The Poynting vector in the far field is
2
20
E , 1ˆS , ,
2
F
r rr
The total power radiated is then given by
2
2 22
00 0 0 0
E ,ˆS sin sin
2
F
radP r r d d d d
Hence we have
2
2
0 0 0
1E , sin
2F
radP d d
Directivity
In dB,
2
S ,,
/ 4r
rad
D rP r
The directivity in a particular direction is the ratio of the power density radiated in that direction to the power density that would be radiated in that direction if the antenna were an isotropic radiator (radiates equally in all directions).
10, 10 log ,dBD D
The directivity of the antenna in the directions (, ) is defined as
Note: The directivity is sometimes referred to as the “directivity with respect to an isotropic radiator.”
Directivity (cont.)
The directivity is now expressed in terms of the far field pattern.
2
S ,,
/ 4r
rad
D rP r
2
20
22
2
0 0 0
E , 12
, 41
E , sin2
F
F
rD r r
d d
Therefore,
2
22
0 0
4 E ,,
E , sin
F
F
D
d d
Hence we have
Directivity (cont.)
Two Common Cases
Short dipole wire antenna (l << 0): D = 1.5
Resonant half-wavelength dipole wire antenna (l = 0 / 2): D = 1.643
y
+h
z
x-h
feed
2l h
Beamwidth
The beamwidth measures how narrow the beam is. (The narrower the beamwidth, the higher the directivity).
HPBW = half-power beamwidth
Gain and Efficiency
The radiation efficiency of an antenna is defined as
radr
in
Pe
P Prad = power radiated by the antenna
Pin = power input to the antenna
The gain of an antenna in the directions (, ) is defined as
, ,rG e D
The gain tells us how strong the radiated power density is in a certain direction, for a given amount of input power.
10, 10 log ,dBG G In dB, we have
Infinitesimal Dipole
The infinitesimal dipole current element is shown below.
x
y
z
Il
The dipole moment (amplitude) is defined as I l.
From Maxwell’s equations we can calculate the fields radiated by this source (see chapter 7 of the textbook).
The infinitesimal dipole is the foundation for many practical wire antennas.
Infinitesimal Dipole (cont.)
0
0
0
0 20
0 20 0
00
I 1 11 cos
2
I 1 1 1( ) 1 sin
4 ( )
I 1 1( ) 1 sin
4
jk rr
jk r
jk r
lE e
r jk r
lE j e
r jk r jk r
lH jk e
r jk r
The exact fields of the infinitesimal dipole in spherical coordinates are
Infinitesimal Dipole (cont.)
0
0
0
0
I( ) sin
4
I( ) sin
4
jk r
jk r
l eE j
r
l eH jk
r
In the far field we have:
0
0
I( )sin
4I
( )sin4
F
F
lE j
lH jk
Hence, we can identify
Infinitesimal Dipole (cont.)
The radiation pattern is shown below.
0
I( )sin
4F l
E j
-9 -3 -6
0 dB
30°30°
60°
120°
150° 150°
120°
60°
Infinitesimal Dipole (cont.)
The directivity of the infinitesimal dipole is now calculated
0
I( )sin
4F l
E j
2
22
0 0
4 E ,,
E , sin
F
F
D
d d
2
22
0 0
4 sin,
sin sin
D
d d
Hence
Infinitesimal Dipole (cont.)
Evaluating the integrals, we have
2
22
0 0
2
2
0
2
3
0
2
4 sin,
sin sin
4 sin
2 sin sin
2sin
sin
2sin
4 / 3
D
d d
d
d
Hence, we have
23, sin
2D
Infinitesimal Dipole (cont.)
23, sin
2D
-9 -3 -6
0 dB
30°30°
60°
120°
150° 150°
120°
60°
, 1.5D
, 1.0D o54.7
0
I( )sin
4F l
E j
The far-field pattern is shown, with the directivity labeled at various points.
Wire Antenna
00
0
II( ) sin
sinz k h z
k h
A good approximation to the current is:
A center-fed wire antenna is shown below.
y
+h
z
I (z)
x-h
feed
2l h
I 0
Wire Antenna (cont.)
00
0
II( ) sin
sinz k h z
k h
A sketch of the current is shown below.
resonant dipole (l = 0 / 2, k0h = / 2)
+h
-h
l
short dipole (l <<0 / 2)
0I( ) I 1z
zh
+h
-h
l
0I( ) I cos2
zz
h
Short Dipole
short dipole (l <<0 / 2)
0I( ) I 1z
zh
+h
-h
l
Wire Antenna (cont.)
The average value of the current is I0 / 2.
0
1I I
2effl l
0
0
I( )sin
4I
( )sin4
effF
effF
lE j
lH jk
Infinitesimal dipole:
0
0
I( )sin
4I
( )sin4
F
F
lE j
lH jk
Short dipole:
Wire Antenna (cont.)For an arbitrary length dipole wire antenna, we need to consider the phase radiated by each differential piece of the current.
Far-field observation point
, ,x y z
00
I 1( ) sin
4jk rl
E j er
0
0
1( )sin I
4
h jk R
h
eE j z dz
R
Wire antenna:
Infinitesimal dipole:
1
22 2 2'R x y z z y
+h
z
x-h
feed
r
R
dz' z'
I (z')
Wire Antenna (cont.)
Far-field observation point
z
y
+h
x-h
feed
r
R
dz'
22 2
2 2 2 2
2 2
2
2
2
'
' 2 '
' 2 '
'1 2
'1 2
R x y z z
x y z z zz
r z zz
z zzr
r r
z z zr
r r r
, ,x y z
Wire Antenna (cont.)
Far-field observation point
z
y
+h
x-h
feed
r
R
dz'
2
'1 2 cos 1 2 cos 1 cos
cos
z z z zR r r r
r r r r
r z
, ,x y z
1 12
xx Note: 1x
cos /z r
Wire Antenna (cont.)
Far-field observation point
z
y
+h
x-h
feed
r
R
dz'
, ,x y z
0
0 0
0
0
cos
0
cos
0
cos0
1( )sin I
4 cos
1( )sin I
4 1 / cos
1( )sin I
4
h jk r z
h
hjk r jk z
h
hjk rjk z
h
eE j z dz
r z
e ej z dz
r z r
ej e z dz
r
Wire Antenna (cont.)
We define the array factor of the wire antenna:
0 cosIh
jk z
h
AF z e dz
We then have the following result for the far-field pattern of the wire antenna:
0
0
1( )sin
4
jk reE j AF
r
Wire Antenna (cont.)
Using our assumed approximate current function we have
0 cos00
0
Isin
sin
hjk z
h
AF k h z e dzk h
The result is (derivation omitted)
0 0 0
20 0
I cos( cos ) cos( )2
sin sin
k h k hAF
k h k
Wire Antenna (cont.)
In summary, we have
0 0 0
20 0
I cos( cos ) cos( )2
sin sin
k h k hAF
k h k
0
0
1( )sin
4
jk reE j AF
r
0
0 0 00
0 0
I cos( cos ) cos( )1( )
2 sin sin
jk r k h k heE j h
r k h k h
Thus, we have
Wire Antenna (cont.)
For a resonant half-wave dipole antenna
0
00
cos cosI1 2
( )2 / 2 sin
jk reE j h
r
0
0
/ 4
/ 2
h
k h
/ 2, 1.643D The directivity is
Wire Antenna (cont.)
Radiated Power:
22
0 0 0
22
0 0 00
0 0 00 0
1E , sin
2
I cos( cos ) cos( )1 1( ) sin
2 2 sin sin
FradP d d
k h k hj h d d
k h k h
0 0 00
0 00 0k
Simplify using
22
0 0 00
0 00 0
I cos( cos ) cos( )1 1( ) sin
2 2 sin sinrad
k h k hP j d d
k h
Wire Antenna (cont.)
Performing the integral gives us
2
0 0 00
0 00
I cos( cos ) cos( )1 12 ( ) sin
2 2 sin sinrad
k h k hP j d
k h
2 2
0 0 0 0
0 0
I cos( cos ) cos( )sin
4 sin sinrad
k h k hP d
k h
The result is then
Wire Antenna (cont.)
The radiation resistance is defined from 2
0
1P I
2rad radR
Z0 Zin
in in inZ R jX
in radR R
Circuit Model
For a resonant antenna (l 0/2), Xin = 0.
y
+h
z
I (z)
x-h
feed
2l h
2
0
2P
Irad
radR
Wire Antenna (cont.)
The radiation resistance is now evaluated.
2
0
2P
Irad
radR
This yields the result
2 2
0 00
0 0
cos( cos ) cos( )1
2 sin( ) sinrad
k h k hR d
k h
2 Dipole: 00,
4 2h k h
73radR
Wire Antenna (cont.)
The result can be extended to the case of a monopole antenna
h
Feeding coax
0 / 4h
1
2monopole dipolein inZ Z
36.5radR
Wire Antenna (cont.)
This can be justified as shown below.
+
-
dipole
Vdipole I0
Virtual ground
+
Vmonopole
I0
-
1
2monopole dipoleV V