OPERATIONAL AMPLIFIER GROUP3 – DEBASHIS BANERJEE JASON PINTO ASHITA MATHEW ECE4430 Project...
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Transcript of OPERATIONAL AMPLIFIER GROUP3 – DEBASHIS BANERJEE JASON PINTO ASHITA MATHEW ECE4430 Project...
OPERATIONAL AMPLIFIER
GROUP3 – DEBASHIS BANERJEE JASON PINTO
ASHITA MATHEW
ECE4430 Project Presentation
DESIGN SPECIFICATIONSTechnology Node – TSMC 0.18µm
Required Design Specifications
Technology node TSMC 0.18µm
Supply (V) 2
Max Power consumption (uW) 150
Differential Gain (dB) 100
CMRR (dB) 100
ICMR (V) 0 - 2.5
Output Swing (V) 0 - 2
Bandwidth - 3dB (kHz) 10
Loading (pF || kOhm) 10 || 100
Slew Rate (V/us) 20
04/21/232 ECE 4430 Project2 Presentation
BMR & BIASING CIRCUIT
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OPERATIONAL AMPLIFIER -TOPOLOGY USED
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Transconductance stabilization circuit
Literature reference : M.M. Ahmadi, R. Lotfi, M. Sharif-Bakhtiar, “A New Architecture for Rail-to-Rail Input Constant-gm, CMOS OperationaI Transconductance Amplifiers ” , ISLPED ‘03
04/21/235 ECE 4430 Project2 Presentation
INITIAL DESIGN STEPS
Redesigned BMR with 5uA reference current Designed short channel biasing circuit Total current budget = 75uA for a max power consumption of
150uW The transconductances of the PMOS NMOS pair of amplifying
devices were made equal by sizing the PMOS to NMOS in the ratio kpn:kpp (5:1)
Current combining stage is made low voltage headroom cascode with floating current sources for proper biasing.
The transconductance stage of diffamp was biased with 5uA each and the summing stage was designed for a current of 30uA
For a rail to rail output swing, we designed a class AB push pull amplifier
Using CC= 0.22CL caused the bandwidth to be about 100Hz only. Compensation capacitor was fine tuned iteratively to achieve a
desired phase margin and maximum bandwidth possible.
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MAGNITUDE- PHASE PLOT
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ICMR : - 0.4 V to 2.23V PHASE MARGIN OVER vcm
90.32dB, -0.41V90.32dB, 2.23V
56 degrees
50.09 degrees
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-0.25 V , 93dB 2.25V, 88dB
OUTPUT VOLTAGE SWING : 0 - 2V
90.32dB, -0.41V 90.32dB, 2.23V
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SLEW RATE
Rise time = 175 nsFall time = 171nsNo ringing observed in output waveform. Settling time =0
Positive slew rate = 9.224 V/usNegative slew rate = -9.275 V/us
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MINIMUM AND MAXIMUM SUPPLY VOLTAGE
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CMRR ACHIEVED = 140dB
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PSRR FOR VDD
PSRR FOR GND
108.8 dB
108.8 dB
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MEASUREMENT OF PSRR
INPUT REFERRED NOISE
35.57nV/sqrt(Hz)
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GAIN BANDWIDTHS
Loaded GBW = 17.36 MHz
Unloaded GBW = 18.04 MHz
Unloaded BW = 434 Hz
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INPUT OFFSET VOLTAGE = -2.01uV
NOMINAL OUTPUT VOLTAGE = 0.8 V
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MEASUREMENT OF INPUT OFFSET VOLTAGE
POWER CONSUMPTION CURVES
with load without load
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PARAMETER SPECS ACHEIVED
1 Differential amplifier topology Folded cascode with modifications
2 Reference topology Drain regulated BMR
3 Minumum Supply Voltage (V) 1.66 V
4 Maximum Supply Voltage (V) 2.84V
5 Gain of differential amplifier (dB) 95dB
6 CMRR (dB) 140dB
7 Reference power consumption (uW) 162 uW
8OpAmp power consumption with zero
input (uW) 144uW
9OpAmp power consumption with no
load (uW) 135uW
10 Total power consumption (uW) 307.1uW
11 Positive Slew Rate (V/us) 9.224V/us
12 Negative Slew Rate (V/us) -9.275V/us
13 ICMR (Vmin ~ Vmax) -0.4V – 2.23V
14 Output Swing (Vmin ~ Vmax) 0-2V
Op-Amp Final Specs and Simulation Results:
15 VDD PSRR (dB) 108.8dB
16 GND PSRR (dB) 108.8dB
17 Nominal output voltage (V) 0.8V
18 Input offset voltage (mV) 0.002mV
19 Unloaded Bandwidth (kHz) 0.434 KHz
20 Loaded Bandwidth (kHz) 0.374KHz
21 Gain bandwidth product (MHz) 17.36MHz
22 Compensation capacitor (pF) 500pF
23 Phase margin (degrees) 58.5 deg
24 Rise time (ns) 175ns
25 Fall time (ns) 171ns
26 Settling time (ns) 0
Input referred noise (V/Hz^0.5) 35.57 nV/sqrt(Hz)
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DEVIATION FROM SPECS
ParameterRequired
Specifications
Specifications acheived
Percentage Error
1Max Power
consumption (uW)
150 144 -4%
2Differential Gain
(dB)100 95 -5%
3 CMRR (dB) 100 140 +28.5%
4 ICMR (V) 0 - 2.5 -0.4 – 2.23 -
5 Output Swing (V) 0 - 2 0-2 0%
6Bandwidth - 3dB
(kHz)10 0.374 -96%
7 Slew Rate (V/us) 20 9.22 -53%
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CONCLUSIONWe observed that increasing the compensation
capacitance improves the phase margin at the cost of bandwidth.
For our case, the degradation in phase margin did not trade off for an appreciable increase in bandwidth.
Better common mode rejection was achieved by cascoding the tail current sources.
A gain of 95dB is not significantly deviated from 100dB because the OPAMP operates mainly as a feedback amplifier.
Since phase margin is high enough, no ringing is observed for a step response
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Questions??
Thank you…
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