Design of Polarization Recon figurable Antenna Using Metasurface

7/24/2019 Design of Polarization Recon figurable Antenna Using Metasurface

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IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 62, NO. 6, JUNE 2014 2891

Design of Polarization Reconfigurable Antenna

Using MetasurfaceH. L. Zhu, S. W. Cheung, Senior Member, IEEE, X. H. Liu, and T. I. Yuk, Member, IEEE

AbstractA planar polarization-reconfigurable metasurfaced

antenna (PRMS) designed using metasurface (MS) is proposed.The PRMS antenna consists of a planar MS placed atop of and indirect contact with a planar slot antenna, both having a circularshape with a diameter of 78 mm (0.9 ), making it compact andlow profile. By rotating the MS around the center with respect tothe slot antenna, the PRMS antenna can be reconfigured to linear

polarization, left-hand and right-hand circular polarizations. Anequivalent circuit is used to explain the reconfigurability of theantenna. The PRMS antenna is studied and designed to operateat around 3.5 GHz using computer simulation. For verification ofsimulation results, the PRMS antenna is fabricated and measured.

The antenna performance, in terms of polarization reconfigura-

bility, axial-ratio bandwidth, impedance bandwidth, realizedboresight gain and radiation pattern, is presented. Results showthat the PRMS antenna in circular polarizations achieves anoperating bandwidth of 3.33.7 GHz (i.e., fractional bandwidth11.4%), a boresight gain of above 5 dBi and high-polarization

isolation of larger than 15 dB. While the PRMS antenna in linearpolarization achieves a gain of above 7.5 dBi with cross-polariza-tion isolation larger than 50 dB.

Index TermsMetasurface (MS), metasurfaced antenna, polar-ization reconfiguration, source antenna.

I. INTRODUCTION

RECONFIGURABLE antenna generally has frequency,radiation pattern, or polarization tunability [1][4].

Since the postures of mobile communications devices in use

are often dynamically changing which creates difficulties

to have good polarization matching for antennas with only

single polarization, it is desirable to have antennas to be able

to work in different polarizations such as linear polarization

(LP) and circular polarization (CP). Study on antennas with

polarization-reconfigurable features has been attracting much

attention [4][20]. In these studies, RF switches such as PIN

diode switches [5][13], [15][20] and MEMS switches [4],

[14] were used to electrically switch polarization of the an-

tennas, thus direct-current (DC) biasing circuits were needed to

bias the PIN or MEMS switches. These switches and biasingcircuits made the whole antennas bulky and high cost. More-

over, the antenna operation would depend on the reliability

of the electronic components used to implement the switches

Manuscript received October 25, 2013; revised January 23, 2014; acceptedFebruary 27, 2014. Date of publication March 06, 2014; date of current version

May 29, 2014.Theauthorsare with theDepartmentof Electrical andElectronicEngineering,

The University of Hong Kong, Hong Kong, China (e-mail: [email protected];[email protected]; [email protected]; [email protected]).

Color versions of one or more of the figures in this paper are available online

at http://ieeexplore.ieee.org.

Digital Object Identifier 10.1109/TAP.2014.2310209

and require DC sources to drive the switches. The electronic

components and circuits may also have adverse effects on the

antennas performances. Electrically reconfigurable antennas

usually have narrow axial-ratio bandwidths (ARBWs) such as

those in [16][19] which had the fractional ARBWs of less

than 5%.

Compared to electrical reconfiguration, mechanical reconfig-

uration is way less popular. To the best knowledge of the au-

thors, there has not been any mechanically operated polariza-

tion reconfigurable antenna proposed. One of the main reasons

is that mechanically reconfigurable antennas require movable

parts. If not designed well, the actuator used to produce the me-chanical movements will be very complicated and occupy much

space, which lead to a bulky and expensive structure. More-

over, change of size and/or shape during tuning is the common

problem for most mechanically reconfigurable antennas. For

these reasons, the polarization reconfigurable antennas studied

so far were all electrical tuning [4][19], [21].

MS, a two-dimensional equivalent of metamaterial, is essen-

tially a surface distribution of electrically small scatterers [22].

With its succinct planar structure and low cost, MS has wide

applications and one of which is on the design of planar an-

tennas with improved performances. For example in [23], [24],

a MS was placed atop of a simple patch/slot antenna to not onlyimprove the gain and return loss bandwidth, but also convert

polarization from LP to CP. The patch/slot antenna (known as

the source antenna in such design) together with the MS was

called a metasurfaced antenna (MS antenna) [23], [24]. In these

designs, there was an air gap between the MS and the source

antenna, which substantially increased the volume of the MS

antenna.

In this paper, as a significant improvement to the work in [23],

[24], a novel polarization-reconfigurable metasurfaced (PRMS)

antenna constructed by placing a MS atop of a slot antenna is

proposed. To make the PRMS antenna compact and low profile,

the slot antenna and MS are placed together in direct contact,

thus eliminating the air gap between them. Results of studies

show that by rotating the MS around the center and relative

to the patch antenna, polarization of the PRMS antenna can

be reconfigured to operate in LP, left-hand circular polarization

(LHCP) and right-hand circular polarizations (RHCP).Compact

size, low cost and simple construction are the apparent advan-

tages of the proposed design. For easy mechanical operation,

the shapes of the slot antenna and the MS are made circular with

the same size. For verification of simulated results, the PRMS

antenna is fabricated and measured using the antenna measure-

ment equipment, Starlab system. Simulated and measured re-

sults show good agreements.

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2892 IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 62, NO. 6, JUNE 2014

Fig. 1. Geometries of (a) MS and (b) slot antenna.

II. DESIGN OF POLARIZATION-RECONFIGURABLE

METASURFACED (PRMS) ANTENNA

The polarization-reconfigurable metasurfaced (PRMS) an-

tenna proposed here consists of a slot antenna (as the source

antenna) and a metasurface (MS). The MS is composed of

corner-truncated square unit cells as shown in Fig. 1(a) on a

single-sided substrate. The same unit cell was used to design a

switchable microstrip antenna in [5] and a 2 2 sequentially

rotated patch antenna array in [25]. Here it is chosen to design

the MS because it has a simple structure and can be specified

using only a few parameters, significantly simplifying the de-

sign work for the PRMS antenna. The slot antenna is designed

on a double-sided substrate as shown in Fig. 1(b) and the MS

are designed to have a circular shape with the same size for

easy mechanical operation. The MS is similar to the MS used

in [24] with the edges of the unit cells at the boundary truncatedto make it circular. Of course, if needed, the PRMS antenna

could also be designed using a rectangular-shaped MS, but this

would be another design. Here, our design purpose is to use

a MS with circular shape for easy mechanical operation. As

will be seen later, polarization reconfigurablity of the antenna

can be accomplished by rotating the MS around the center

relative to the slot antenna. The rotation angle is measured

from the -axis as shown in Fig. 1(a). Studies have shown that

with and 90 , the PRMS antenna is left-hand cir-

cular polarization (LHCP) and right-hand circular polarization

(RHCP), respectively. Since the MS at is a mirror

image of itself at , the performances of the antennain RHCP and LHCP should be identical. With and

135 , the PRMS antenna is linear polarization (LP) along the

-axis, same with that of the source slot antenna. Fig. 2 shows

polarization of the antenna at , 45 , 90 , and 135 .

In assembling the PRMS antenna, the non-copper side of the

MS is placed atop the slot antenna and is in direct contact with

the feed-line (top side) of it as shown in Fig. 3. This leads to a

very compact and low profile structure. An SMA connector is

used to feed to the feed-line through the ground plane and sub-

strate material of the slot antenna. The PRMS antenna together

with the SMA connector is studied and designed using the EM

simulation tool CST on a Rogers substrate RO4350B, having a

thickness of 1.524 mm and a dielectric constant of .

The design procedure can be divided into the following steps:

Fig. 2. Antenna polarization at different rotation angles .

Fig. 3. Assembly schematic of PRMS antenna.

TABLE IDIMENSIONS OFFRMS ANTENNA (Unit: mm)

1) Design the slot antenna to have a wide operating band at

around 3.5 GHz.

2) Add the MS atop the slot antenna (which will change the

characteristic of the antenna) and then optimize the PRMS

antenna in terms of S11 using the dimensions of the radi-

ator and feed line.

3) Optimize the ARBW using the dimension of the MS.

The dimensions of thefinal design are listed in Table I which

is used to fabricate the PRMS antenna shown in Fig. 4 for mea-

surement using the antenna measurement equipment, Satimo

Starlab system.

III. ANALYSIS OF PRMS ANTENNA

A. Parametric Study

As mentioned previously, the truncated-corner unit cell used

to design our MS can be specified using only a few parameters.

This can significantly simplify the design work of the PRMS.

Computer simulation has shown that there are only three pa-

rameters in the unit cell of Fig. 1(a) having significantly effects

on the antenna performance. They are the width of the unit

cell, the side of the triangle, and the spacing between the

unit cells. Thus parametric studies of these parameters on the


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ZHUet al.: DESIGN OF POLARIZATION RECONFIGURABLE ANTENNA USING MS 2893

Fig. 4. (a) Top view of prototyped slot antenna, (b) bottom view of prototyped

slot antenna, and (c) prototyped metasurface.

axial ratio (AR) are carried out on the proposed PRMS antenna

with LHCP. The results are shown in Fig. 5 where the green

lines show the AR of the proposed PRMS antenna using the

parameters of Table I. It can be seen that the proposed PRMS

antenna has a AR bandwidth (ARBW) for dB from 3.3

to 3.7 GHz, two dips of 0.9 and 0.5 dB at 3.4 and 3.65 GHz,

respectively, and a peak of 1.7 dB at 3.53 GHz between the two

dips.As decreases from 20 mm to 18.5 mm, Fig. 5(a) shows

that the high- and low-frequency dips shift up from 3.18 and

3.56 GHz to 3.4 and 3.65 GHz, respectively, with the frequency

spacing between the two dips reduced from 380 to 250 MHz.

The peak between two dips shifts from 3.4 to 3.53 GHz with

amplitude dropped from 4.7 to 1.7 dB, respectively, resulting

in a large ARBW of 400 MHz. When decreases further to

17 mm, the two dips merge together with a minimum AR of

0.7 dB at 3.68 GHz. The antenna has an AR frequency band (for

dB) from 3.5 to 3.82 GHz, with the ARBW reduced

to 320 MHz. Thus, the parameter can be used to adjust the

frequency band of AR. Fig. 5(b) shows the AR with differentvalues of . It can be seen that as increases from 4.6 mm to

5, 5.3, and 5.6 mm, the AR at the frequency of 3.5 GHz drops

continuously. The two dips of AR move towards each other and

thus the ARBW reduces. When continues to increase to 6 mm,

the two dips merge together with a minimum AR of 1.2 dB at

around 3.5 GHz. Note that as changes, the frequency band for

dB is not changed much, with the center frequency

remained at about 3.5 GHz, unlike the case of changing in

Fig. 5(a). Thus the parameter can be used to slightly tradeoff

the value of AR against ARBW. TheAR with different values of

is shown in Fig.5(c).It can be seenthat has the similar effects

to , but in an opposite way. When increases from 0.5 mm to

0.75, 1 and 1.5 mm, the two dips in AR move towards each other

and the peak between them drops. The ARBW decreases with

Fig. 5. Simulated AR with different (a) , (b) , and (c) .

the AR within the AR frequency band reduced. Thus, can also

be used to slightly tradeoff the value of AR against ARBW.

Since the MS at and 90 for RHCP and LHCP,

respectively, of the MS are the mirror images of each other, the

results of parametric study on AR for RHCP should be the same

as those of LHCP.

B. Equivalent Circuit of MS

Here we use an equivalent circuit to explain how theproposed

PRMS antenna can have different polarizations when the MS

is rotated. In Fig. 1(a), the slot antenna is linear polarization

along the -axis. To start this, the MS in Fig. 1(a) is redrawn in

Fig. 6(a) where the pattern enclosed by the blue square can be

regarded as a new unit cell on the same MS. For convenience in

description, the new unit cell is enlarged and shown in Fig. 6(b).

When the MS is placed atop the slot antenna which is linear


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Fig. 6. (a) MS, (b) new unit cell with diagonal corner truncated, and (c) new

unit cell without truncation.

polarization along the -axis, an -field will be developed along

the -axis as shown in Fig. 6(b). The -field can be resolved

into two orthogonal components and as shown in the

same figure. If the diagonal corners of the unit cell were not

truncated as shown in Fig. 6(c), due to the symmetrical structure,

the orthogonal components and would see the MS as

an identical RLC circuit shown in Fig. 6(c) with an impedance

given by

(1)

where and are the inductance and resistance, respectively,

of each patch, is the capacitance created by the gaps between

two adjacent and opposite patches. However, if the diagonal cor-

ners are truncated as in our proposed MS shown in Fig. 6(b),

and will see two different impedances and , respec-

tively, which can be written as

(2)

(3)

Truncating the corners widens the gaps between the adjacent

and opposite patches and hence increases the value of in

(2), making less capacitive than . Thus, we can use the di-

mensions of the truncated corners (which is determined by the

parameter in Table I) to vary the phase difference between

and . If the MS is designed such that and

, then and .

will lead by 90 and the resultant -field throughthe MS

will be LHCP and rotating in the clockwise direction as indi-

cated by the yellow arrowed arc in Fig. 6(b). To reconfigure the

antenna to RHCP, we can simply rotate the MS by , so

that the value of in (3) becomes larger and will lead

by 90 instead. When the rotation angle is or 135 ,

the unit cell is symmetrical along the and axes as shown in

Fig. 7. Thus, both and see an identical impedance and

so have the same amplitude and phase after going through the

MS. The PRMS antenna remains LP.

IV. SIMULATION ANDMEASUREMENT RESULTS

A. Reflection Coef ficient S11

The final design of proposed PRMS antenna has been studied

using computer simulation and measurement. The simulated

Fig. 7. E-field for (a) and (b) .

and measured S11 of the antenna with different rotation angles

are shown in Fig. 8. It can be seen that the simulated and

measured results agree well. Since the MS at and 90

are the mirror images of each other, the simulated S11 for LHCP

and RHCP are identical as shown in Fig. 8(a) and (c), respec-

tively. The simulated frequency band (for dB) are

more than from 34 GHz. The measured S11 at these two rota-

tion angles are not exactly the same because of the fabrication

and measurement tolerances. At for LP, Fig. 8(b)

shows that the frequency band shifts down slightly and is from3 to 3.76 GHz for simulation and 3.74 GHz for measurement.

However, at , Fig. 8(d) shows that the S11 frequency

band shifts up slightly, from 3.28 to 4 GHz for simulation and

from 3.3 to 4.2 GHz for measurement.

B. Axial Ratio (AR)

The simulated and measured ARs in the boresight (along

axis as shown in Fig. 1) of the PRMS antennas are shown in

Fig. 9, where it can be seen that the simulated and measured re-

sults agree well. Again, because of mirror images of each other,

the simulated ARs with and 90 are identical but

with orthogonal polarizations as shown in Figs. 9(a) and (c), re-spectively. The simulated and measured ARs are less than 3 dB

from 3.33.7 GHz for both LHCP and RHCP, with an ARBW

of 400 MHz (or a fractional bandwidth of 11.4%). The ARBW

is narrower than the impedance bandwidth dB in

CP showed in Fig. 8(a) and (c), and thus becomes the operating

bandwidth of the antenna. With and 135 when the

antenna is operated in LP, Fig. 9(b) and (d) show that the simu-

lated ARs are larger than 40 dB from 3 to 4 GHz, indicating very

high linear polarization purity. Since the antenna measurement

equipment, the Satimo Starlab System, can measure the AR of

CP antennas only up to 20 dB, the measured result is therefore

a horizontal straight line at 20 dB in Fig. 9(b) and (d).

C. Ef ficiency and Realized Gain

The efficiencies of the PRMS antenna with different are

shown in Fig. 10. It can be seen that the simulated and measured

results agree well. The simulated and measured efficiencies of

the antenna at all rotation angles tested are above 80% across

the operating bandwidth (3.33.7 GHz).

The simulated and measured realized boresight gains of the

PRMS antenna are shown in Fig. 11. Again, good agreements

between simulated and measured results in the co-polarization

and cross-polarization can be seen.

Fig. 11(a) and (c) shows that the realized boresight gains

of the antenna in LHCP and RHCP in the operating band-

width of 3.33.7 GHz are above 5 dBi, with cross-polarization


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Fig. 8. Simulated and measured S11 for (a) , (b) , (c)

, and (d) .

of less than 10 dBi. This suggests high cross-polarization

isolation (XPI) of larger than 15 dB, i.e., good polarization

Fig. 9. Simulated and measured ARs for different rotation angles.

purity. Fig. 11(b) and (d) show that when the MS is rotated to

and 135 , (i.e., the PRMS antenna is LP), the realized

boresight gains are higher than 7.5 and 6 dBi, respectively,


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Fig. 10. Simulated and measured efficiencies for different rotation angles.

at the operating bandwidth for both simulated and measured

results. Since XPI for LP are less than 50 dB, it is too small

to be shown in the same figures

Fig. 11. Simulated and measured realized gain for different .

D. Radiation Pattern

The simulated and measured radiation patterns of the PRMS

antenna at 3.5 GHz for different are shown in Fig. 12. For


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Fig. 12. Simulated and measured radiation patterns at 3.5 GHz for different

. (a) -plane; (b) yz-plane; (c) -plane;(d) yz-plane; (e) -plane; (f) -plane; (g)

xz-plane; (h) -plane.

comparison, the radiation patterns of the slot antenna alone are

also shown in the same figures. It can be see that the antenna has

unidirectional radiation patterns, instead of bidirectional radia-

tion pattern typically for single slot antenna. This phenomenon

was already found in [24]. For the co-polarization patterns in

CP in Fig. 12(a), (b), (e), and (f), the front-to-back ratios (FBRs)

are all large than 12 dB. For the radiation patterns in LP shown

in Fig. 12(c), (d), (g) and (h), the FBRs are larger than 15 dB,

where the cross-polarizations are too small to be shown and so

omitted. The results in Fig. 12 show that the MS receives the LP

signal from the source slot antenna and reradiates the signal in

CP ( or 90 ) or LP ( or 135 ) to the other side

in the opposite direction (along axis as shown in Fig. 1).

V. CONCLUSIONS

A PRMS antenna designed using a slot antenna and a MS has

been presented. The polarization of the antenna can be mechan-

ically reconfigured to LHCP, RHCP and LP by rotating the MS

around the center with respect to the slot. The polarization-re-

configurable property has been analyzed and explained using an

equivalent circuit. The simulated and measured performances in

terms of polarization reconfigurability, efficiency, gain and radi-

ation pattern, have been presented. Results have shown that the

polarization reconfiguration can be achieved at around 3.5 GHz

with a fractional operating bandwidth 11.4%.

REFERENCES

[1] D. Peroulis, K. Sarabandi, and L. P. B. Katehi, Design of reconfig-urable slot antennas, IEEE Trans. Antennas Propag., vol. 53, no. 2,

pp. 645654, Feb. 2005.

[2] R. L. Haupt and M. Lanagan, Reconfigurable antennas, IEEE An-tennas Propag. Mag., vol. 55, no. 1, pp. 4961, Feb. 2013.

[3] O. H. Karabey, S. Bildik, S. Bausch, S. Strunck, A. Gaebler, andR. Jakoby, Continuously polarization agile antenna by using liquid

crystal-based tunable variable delay lines, IEEE Trans. AntennasPropag., vol. 61, no. 1, pp. 7076, Jan. 2013.

[4] T. J. Jung, I. J. Hyeon, C. W. Baek, and S. Lim, Circular/linear po-larization reconfigurable antenna on simplified RF-MEMS packaging

platform in K-band, IEEE Trans. Antennas Propag., vol. 60, no. 11,pp. 50395045, Nov. 2012.[5] Y. J. Sung, T. U. Jang, and Y. S. Kim, A reconfigurable microstrip

antenna for switchable polarization,IEEE Microw. Wireless Compon.Lett., vol. 14, no. 11, pp. 534536, Nov. 2004.

[6] H. Aissat, L. Cirio, M. Grzeskowiak, J. M. Laheurte, and O. Picon,Reconfigurable circularly polarized antenna for short-range commu-

nication systems, IEEE Trans. Microw. Theory Tech., vol. 54, no. 6,

pp. 28562863, Jun. 2006.[7] W.Yi-Fan, W.Chun-Hsien, D.Y. Lai,and C.Fu-Chiarng, Areconfig-

urable quadri-polarization diversity aperture-coupled patch antenna,IEEE Trans. Antennas Propag., vol. 55, no. 3, pp. 10091012, Mar.

2007.[8] K. Boyon, P. Bo, S. Nikolaou, K. Young-Sik, J. Papapolymerou, andM.

M. Tentzeris, A novel single-feed circular microstrip antenna with re-

configurable polarization capability,IEEE Trans. Antennas Propag.,vol. 56, no. 3, pp. 630638, Mar. 2008.

[9] C. Rui-Hung and R. Jeen-Sheen, Single-fed microstrip patch antennawith switchable polarization,IEEE Trans. Antennas Propag., vol. 56,

no. 4, pp. 922926, Apr. 2008.[10] W. M. Dorsey, A. I. Zaghloul, and M. G. Parent, Perturbed square-ring

slot antennawith reconfigurablepolarization,IEEE Antennas Wireless

Propag. Lett., vol. 8, pp. 603606, 2009.[11] A. Khaleghi and M. Kamyab, Reconfigurable single port antenna with

circular polarization diversity,IEEE Trans. Antennas Propag., vol. 57,no. 2, pp. 555559, Feb. 2009.

[12] Q. Pei-Yuan,A. R. Weily, Y. J. Guo,and L. Chang-Hong, Polarizationreconfigurable U-slot patch antenna, IEEE Trans. Antennas Propag.,

vol. 58, no. 10, pp. 33833388, Oct. 2010.[13] S. Youngje, Investigation into the polarization of asymmetrical- feed

triangular microstrip antennas and its application to reconfigurable an-

tennas,IEEE Trans. Antennas Propag., vol. 58, no. 4, pp. 10391046,Apr. 2010.

[14] A. G. Besoli and F. De Flaviis, A multifunctional reconfigurable pix-eled antenna using MEMS technology on printed circuit board,IEEE

Trans. Antennas Propag., vol. 59, no. 12, pp. 44134424, Dec. 2011.


8/8


[15] M. S. Nishamol, V. P. Sarin, D. Tony, C. K. Aanandan, P. Mohanan,and K. Vasudevan, An electronically reconfigurable microstrip an-

tenna with switchable slots for polarization diversity,IEEE Trans. An-

tennas Propag., vol. 59, no. 9, pp. 34243427, Sep. 2011.[16] R. Jeen-Sheen and S. Chuang-Jiashih, Polarization-diversity ring slot

antenna with frequency agility,IEEE Trans. Antennas Propag., vol.60, no. 8, pp. 39533957, Aug. 2012.

[17] R. Jeen-Sheen, L. Wang-Lin, and C. Tsair-Rong, Circular polariza-tion and polarization reconfigurable designs for annular slot antennas,

IEEE Trans. Antennas Propag., vol. 60, no. 12, pp. 59986002, Dec.2012.

[18] Y. Xue-Xia, S. Bing-Cheng, Y. Fan, A. Z. Elsherbeni, and G. Bo,

A polarization reconfigurable patch antenna with loop slots on theground plane, IEEE Antennas Wireless Propag. Lett., vol. 11, pp.

6972, 2012.[19] A. Khidre, L. Kai-Fong, Y. Fan, and A. Z. Elsherbeni, Circular po-

larization reconfigurable wideband E-shaped patch antenna for wire-less applications, IEEE Trans. Antennas Propag., vol. 61, no. 2, pp.

960964, Feb. 2013.

[20] S. Raman, P. Mohanan, N. Timmons, and J. Morrison, Microstrip-fedpattern- an d polarization- reconfigurable compact truncated monopole

antenna,IEEE Antennas Wireless Propag. Lett., vol. 12, pp. 710713,2013.

[21] J. A. Ruiz-Cruz, M. M. Fahmi, S. A. Fouladi, and R. R. Mansour,Waveguide antenna feeders with integrated reconfigurable dual cir-

cular polarization, IEEE Trans. Microw. Theory Techn., vol. 59, no.12, pp. 33653374, Dec. 2011.

[22] C.L. Holloway, E.F. Kuester, J. A.Gordon,J. OHara, J. Booth, andD.

R. Smith, An overview of thetheory and applications of metasurfaces:The two-dimensional equivalents of metamaterials, IEEE Antennas

Propag. Mag., vol. 54, no. 2, pp. 1035, Apr. 2012.[23] H. L. Zhu, K. L. Chung, X. L. Sun, S. W. Cheung, and T. I. Yuk, CP

metasurfaced antennasexcited by LP sources, inProc. IEEE Antennas

Propag. Soc. Int. Symp. (APSURSI), 2012, pp. 12.[24] H. L. Zhu, S. W. Cheung, K. L. Chung, and T. I. Yuk, Linear-to-

circular polarization conversion using metasurface, IEEE Trans. An-tennas Propag., vol. 61, no. 9, pp. 46154623, Sep. 2013.

[25] W. Zhongbao, F. Shaojun, F. Shiqiang, and J. Shouli, An InmarsatBGAN terminal patch antenna array with unequal input impedance

elements and conductor-backed ACPW series-feed network, IEEE

Trans. Antennas Propag., vol. 60, no. 3, pp. 16421647, Mar. 2012.

H. L. Zhureceived the B.Eng. degree in information

engineering, and the Masters degree in electromag-

netic field and microwave engineering from Beijing

Institute of Technology, Beijing, China, in 2009

and 2011, respectively. He is currently working

toward the Ph.D. degree in electrical and electronic

engineering at the University of Hong Kong, Hong

Kong, China.

His research interests include antenna design and

study of metasurface.

S. W. Cheung (M89SM02) received the B.Sc.degree with First Class Honours in Electrical and

Electronic Engineering from Middlesex University,

London, U.K. in 1982 and the Ph.D. degree fromLoughborough University of Technology, Lough-

borough, U.K., in 1986.From 1982 to 1986, he was a Research Assistant

in the Department of Electronic and Electrical En-gineering, Loughborough University of Technology,

where he collaborated with the Rutherford AppletonLaboratory and many U.K. universities to work a

project fo r new generations of satellite systems. He is an Associate Professor at

the University of Hong Kong and in charge of the Microwave, RF Frequencyand Telecom Laboratories. His current research interests include antenna

designs, 2G, 3G, and 4G mobile communications systems, MIMO systems,and satellite communications systems.

Dr. Cheung has been serving the IEEE in Hong Kong for the past twentyyears. In 2009 and 2010, he was the Chairman of the IEEE Hong Kong Joint

Chapter on Circuits and Systems and Communications. He was the Honorary

Treasurer and currently the Chair-Elect of the IEEE Hong Kong.

X. H. Liu received B.Eng. degree in photoelectricinformation engineering from Shenzhen University,

Shenzhen, China, in 2008 and the M.Sc. degreein electrical and electronic engineering (communi-

cations engineering stream) from The Universityof Hong Kong, Hong Kong, China, in 2013. His

research interests include antenna design and the

study of metasurface

T. I. Yukreceived the B.S. degree from Iowa State

University, Ames, IA, USA, in 1978 and the M.S.and

Ph.D. degrees from Arizona State University, Tempe,

AZ, USA, in 1980 and 1986, respectively.

Since 1986, he has been teaching at the Universityof Hong Kong. His current research interests include:

wireless communications, and antenna designs.

Design of Polarization Recon figurable Antenna Using Metasurface

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