Refresher Course in Transistor Combined
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Transcript of Refresher Course in Transistor Combined
-
Refresher course in transistor circuits
Dr N HarrisSchool of Electronics and Computer Science
(Based on notes by Dr Neil Ross for ELEC2012And me for ELEC1005 if you want more detail)
-
Course Contents and Aims
Brief Revision of Bipolar Transistors Brief Revision of Field Effect Transistors Common configurations Biasing Small signal analysis Useful analog techniques
Differential amplifer Current mirrors Active loads
Op Amps (whats in them) Multipliers Assignment
Aim: To refresh your understanding of transistors and basic uses,and how to simulate circuits
-
The aim is to understand things like this
-
You will require Spice to do the assignment
Spice is a circuit simulation package Available from many different sources A good free one is available from Linear Technology
Its called LTSpice Get it from here
http://www.linear.com/designtools/software/
Other Spice is available on departmental computers egOrcad/Cadence
-
Bipolar transistors
C
B
E
C
B
E
n
p
n
p
n
p
Familiar?
But what is really happening inside?
Lets try and find out!
Notice that the construction of the transistor looks like 2 diodes back toback.
Its made of n and p doped silicon.
We start by looking at a pn diode:-
-
Ideal PN Diode
Defined by the diode equation
= 1kT
Vq
S eII
Is is called the saturation current of the diode.V is the applied voltageq is the charge on an electron - 1.6 x10-19Ck is the Boltzmann constant 1.38 x 10-23J/KT is the absolute temperature
-
= 1kT
Vq
S eII
kT/q = 25.3mV @ 20 degrees C = 25.8mV @ 27 degrees C Often a value of 25mV is assumed for numerical convenience
Is itself is very temperature dependant
A typical value for Is is 10-14 A at room temperature.
-
Diode Curve
1mA
2mA
0.64V
50mV
10-14 A
I
V
= 1kT
Vq
S eII
The slope at any point represents a conductance,(1/R). As the slope varies, we term this a dynamicconductance. The inverse of this is a dynamic resistance
-
A bit about Notation
Large Signal (DC) Capital letters eg IC DC collector current
Small Signal (AC) Lower case letters eg ic AC collector current
Instantaneous total signal Combination eg Ic
Useful as transistor circuits are analysed in 2 chunks
-
Bipolar Transistors - definitions
N NPiE
iBiC
Emitter Collector
Base
P PNiE
iBiC
Emitter Collector
Base
B
C
E
vBC
vBE vBE
iC
iBiBiE
vBC
C
E
BiC
iE
NPN PNP
-
N NPiE
iBiC
Emitter Collector
Base
P PNiE
iBiC
Emitter Collector
Base
B
C
E
vBC
vBE vBE
iC
iBiBiE
vBC
C
E
BiC
iE
NPN PNP
Direction of Conventional Current (holes)(Electrons go The other way)
Bipolar Transistors - definitions
-
Main points to remember The transistor can be thought
of a current source. The collector current is independent of collector-base voltage
The emitter current is controlled by the base-emitter voltage
The emitter current and the collector current are nearly the same (base current small)
Collector current is therefore controlled by the base-emitter voltage
-
So what?
+ +
R
Add a load resistor
A small voltage change Vi between emitter and base causes a current changeIE. If all this current passes to the collector, then the output voltage changesby IE.R. Basically it is controlled by R (within reason!)
Specifically, A=Vo/Vi=(R IE)/(r IE )=R/r where r is the dynamic resistance of the base-emitter junction and is usually low (1000s of ohms), but sadly, as its dynamic,changes its value with applied voltage (so not linear)
E
B
C
P N P
-
Transistor
This is the basis of transistor action. Power gain has been achieved as the voltage is increased although the current hasnt changed much.(VI is bigger)
Current in the low resistance input circuit has been transferred to the high resistance output circuit.
Transistor= transfer resistor
-
However, not all the current gets from the emitter to the collector. Some is lost in the base due to
recombination. is the fraction of the emitter current reaching the collector. Usually quite close to 1
IE IC
IB++
EB junction CB junctionReverse biasForward bias
Conventional current
-
relates to the fraction that is lost. can be a large number and is very useful
IE IC
IB++
EB junction CB junctionReverse biasForward bias
P PN
-
What about a NPN device?
Best considered with Electron Current (go the other way to conventional current - holes)
IE IC
IB+ +
BE junction CB junctionReverse biasForward bias
N P N
The bias potentials are the other way round, and the flow shows themajority carriers (in this case electrons)
-
What about a NPN device?
Now considered with Conventional Current (holes)
IE IC
IB+ +
BE junction CB junctionReverse biasForward bias
N P N
Can be considered that IC and IB go in and add up to IE
-
Can be thought of as a current controlled valve
Base current can be used to program a collector current
The fraction of the emitter current flowing in the collector is called the alpha () of the transistor
is called the common base current gain < 1, but 1-
-
A bit more on Beta from Kirchoff
C
CCECB
ECB
i
iiiii
iii
=
+==
=++
1
0
Therefore
=
=
1BC
ii
Which is sometimes called hfe
-
Beta (cont)
Note also that
+
=
1Beta is called the common emitter current gainIt is one of the main manifestations of gain in the transistor.Eg if =0.99, beta=0.99/(1-0.99)=99For every microamp of base current, we get 99 microamps of collector current
It is a current amplifier
iC=iBVery Important!
-
Common Emitter cct-Base circuit
IB
VBE
(A)
102030
0.5 1
VCE>1VB
EvBE
iC
iBiE
C
VBE
VCERL
Lets wire up a transistor and have a look.
We have an input circuit (base) and an output circuit (collector) with a common emitter. The input looks like a diode (as expected)
-
Emitter circuitIC
1234
1 2 3 4 5VCE
mA
iB=10A
iB=20A
iB=30A
iB=40AActive Region
Saturation Region
B
EvBE
iC
iBiE
C
VBE
VCERL
The output looks like a constant current source, but dependent on ib
(Remember transistor action)
-
Current gain (or F)
Maximum value of is at 10-20 mA for discrete transistors and 0.05-0.5 mA for IC transistors
-
IC
1234
1 2 3 4 5VCE
mA
iB=10A
iB=20A
iB=30A
iB=40AActive Region
Saturation Region
The Early voltage
Vea
Collector voltage has a small effect on collector current. Width of Base reduces, collector current increases (Vea~70V).
-
Transistor characteristics
Notice non-linearity with input voltage
-
Generic FET operation
The generic FET can be considered to be a semiconducting material with a connection at either end (Drain and Source), with its resistance modulated by the electric field applied perpendicularly at the gate.
It can also be considered as a long PN junction, with lateral conduction, so the depletion zone increases as you cross the device
NS D
Field P
V
Depletion Zone
-
Types of Field Effect Transistors
Junction Field Effect transistor (JFET) Important in historical development
Not used much these days
Metal Oxide Semiconductor FET (MOSFET) Mostly used for logic circuits
Also used for power circuits (Power MOSFET)
Increasingly used for Analogue IC design in CMOS processes along with Digital IC
-
FET operation
In both the JFET and MOSFET, the operation is basically the same.
The number of carriers in a conducting channel is controlled by a lateral gate
The details of operation are quite different in both cases but they are both operating effectively as variable resistors
-
MOSFET structure
Consider an n-channel device:
N+ N+
P
PolysiliconOxide
B
S G D
Channel
-
DS
G B
D
S
G B
D
S
G B
D
S
G B
N depletion N enhancement
P depletion P enhancement
MOSFET Schematic Symbols
-
Notes on MOSFETs
The MOSFET is a 4 terminal device, not three.
For discrete devices, the substrate (B) is normally connected to the source to effectively give a three terminal device
MOSFETs can be of two forms: depletion : conducting when VGS=0
enhancement : non-conducting when VGS=0
-
ID
VDS
Region 1 Region 2
VGS increasing
VT+1
VT+2
VT+3
VT+4
DC characteristics of FETs
Fortunately, we can use the same basic model for both types of device.
n-channel device
Note: for depletion device: VT < 0for enhancement device: VT > 0
Saturation region
Linear region
IC
1234
1 2 3 4 5VCE
mA
iB=10A
iB=20A
iB=30A
iB=40AActive Region
Saturation Region
Compare with bipolar
-
ID
VGS
Region 2i.e. VDS large
VTD VTE
Depletion DeviceJFET or MOSFET
Enhancement MOSTonly
VT is the threshold voltage.
The voltage at which the devicestarts to conduct
FET Input Curves they are quadratic, not exponential
-
IC
VCE
IB increasing
IC
VBE
VCE large
Compare with bipolar
-
DC Characteristics of FETS
Region (1) is much smaller in bipolar device (
-
DC Characteristics of FETS
Bipolar is an enhancement type device (in FET terms)
Negligible gate current flows for FETS Note different terminology for saturation for the two types of device
-
Mathematical Description
In region (2), beyond pinchoff,
This is only valid for VGS-VT 0 ie VGS VTAlso only valid for VDS VGS-VT ie region 2 Notice that we have two parameters to describe the FET, K and VT.
( )22 TGSD
VVKI =VDS
Region 1 Region 2
VGS increasing
VT+1
VT+2
VT+3
VT+4
VDS
Region 1 Region 2
VGS increasing
VT+1
VT+2
VT+3
VT+4
-
Mathematical Description
VT is called the threshold voltage K has the dimensions A/V2 and is called the device constant or beta of the device.
For the MOSFET the parameter is called KP
For a JFET the parameter is called BETA
We avoid using the term beta in this context to remove the possibility of confusion with bipolar.
-
Mathematical Description
In region (1), we have a different equation
K and VT are the same as before. We still have the restriction VGS-VT 0 This time the restriction on VDS is 0 VDSVGS-VT
( )
=
2.
DSTGSDSD
VVVVKI
VDS
Region 1 Region 2
VGS increasing
VT+1
VT+2
VT+3
VT+4
VDS
Region 1 Region 2
VGS increasing
VT+1
VT+2
VT+3
VT+4
-
Basic transistor circuits
Emitter is common to input and output
-
Basic transistor circuits
Collector is common to input and output
-
Basic transistor circuits
Base is common to input and output
-
Consider the Common Emitter configuration -Transfer Function for DC
vBE
iC
iB VCE=Vout
RL
vS
RS
VCC
vout
vinvB
0.6V
SRLRSlope =
-
Example using Pspice
-
So how do we use this as an amplifier? The Problem
We want to amplify a small signal We cannot apply it direct to our amplifier Why?
RL
vin
RS
vout
vout
vinvB
-
Applying an AC signal results in different outputsDepending on bias (or offset)
Input signals
Output signals
-
Basic Biassing
For AC we can couple through a capacitor
RL
vin
vout
RB
C
LCCCOUT
BC
B
BECCB
RIVVII
RVV
I
=
=
=
Let Vin = 0
Now apply VinTransistor is already in the active region
A small bias current always flows through RB
-
Simple bias circuit more detailAssume VBE = 0.6 V
B
C
B
CCCout
CB
CCCCCCQCCout
BQCQ
B
CCBQ
BBCC
RR
RRVV
RR
VVRIVV
IIR
VI
RIV
6.01
6.0
6.06.0
+
=
==
=
=
+=
Q-point depends on the value of - not very good!
RL
vin
vout
RB
C
-
Simple bias circuit
=100 =50
-
Traditional Preferred Bias Technique (Emitter biasing)
R1 and R2 form a potential divider providing a fixed VBVB becomes VBE+IERE
RE provides a form of negative feedback. As IE increases, IERE increases,and VBE falls, which results in IERE falling as well
-
DC Analysis (Quiescent Point)
1) Replace R1 and R2 by the Thevenin equivalent
RLCC2
VCC
RE
RTH
VTH
VOUT
RTH=R1//R2And VTH=VCC R2/(R1+R2)
TH
BTHB R
VVI =
We also make the assumption
-
( )( )( )
( )( )
( ) EBETH
ETH
BETHBC
ETH
BETHB
BETHETHB
EBBTHTHBE
THBTHB
RVV
RRVV
II
RRVV
I
VVRRIRIIRVV
RIVV
++
==
++
=
=++
+=
=
1
1
11
TH
BTHB R
VVI =From
BEEB VVV =From
Small compared with
Hence IC is largely independent of
=
B
CCC R
VI 6.0Compared to simple method
-
Improved bias circuit
-
Improved bias circuit
=100 =50
-
Small signal Models
Having biased the transistor, we need to know the gain for our signalsof interest.
Small signal model is used. It only works for small signals, as thesmall signal model assumes a straight line fit to the transistor curvesi.e it is linearised around the operating point.
Small signal analysis is very important, particularly for designing andunderstanding IC design techniques.
Its all about trying to make a non-linear expression linear.
This makes analysing it much easier as we can use the common andwell known techniques of network theory, such as superposition, and Norton and Thevenin theorems.
-
Transistor Curves (What is the gain for a small signal?)
vBE
iBVBE Slope=1/r
vBE
iCVBE Slope=gm
Base Collector
BC II =RememberWe assume a straight line atthe Q point, as shown.The output current looks likeas shown in the second graph
We can see why there is no gain for low iB. A large variation in VBEproduces very little variation in iC.
-
kTqv
SC
BE
eIi =
BE
C
dvdi
Now
And the slope is given by
vBE
iCVBE Slope=gm
But we know that we are operating at the quiescent pointso we set the ac or small signal to zero as
cCC iIi +=and ic=0, therefore iC=IC
Note that gm is different depending on where you are on the curve.
We need the slope at the operating point
Total current = DC + AC
And so the top equation applies
-
So
kTqI
eIkTq
dvedI
dvdi CkT
qV
S
IiBE
kTqv
S
IiBE
CBE
Cc
BE
Cc
===
=
=
BecausekT
qV
SC
BE
eII =
This is the slope at the Q point and is therefore the mutual conductance
m
C gkTqI
=
Basically the diode equation
This is the definition of DC current
Note only dependent on DC conditions
-
Refer back to the base
BC II =Remembering Therefore the input slope isr
gkTqI
slope mC 11 ===
vBE
iBVBE Slope=1/r
Giving the input resistance r as
pi
r
gr
m
==
-
Basic Hybrid PI Modelb c
gmvbe
e
rp
m
Cm
gr
qkTI
g
pi =
=
Basis of small signal analysis ignores the DC conditions
Note that small in this case means less than 25mV
-
It is the same as this -
b c
hfeib
e
rp
ib
bbmbem
beb
iirgvgvri
pipi
=
feh
The difference is that in this case,the output makes use of a currentdependent generator rather than a voltage dependent one.
-
Small Signal FET model
In region (2), FETS behave like a voltage controlled current source, just like a bipolar.
Therefore we can use the same small signal equivalent circuit:
gmvgs
vg
g d
sNote that because there is no gateCurrent, rpi disappears
Gm is much lower in FETs
-
High frequency Hybrid pi model
Rx is the spreading resistance (~150)
The capacitances lead to non-ideal performance (high frequency limitations)
-
Application of the Small signal model Consider our simple common emitter cct with simple biasing
What is the small signal gain?
VCC=5RB=820KohmRC=2.2Kohm =200
VBE=0.6V
Common Emitter Amplifier
-
Determine the DC bias condition
( )
V
RVVRV
RIVV
mAR
VVI
AR
VVI
B
BECCCCC
CBCCC
B
BECCC
B
BECCB
64.236.25
07.1
36.5
=
=
=
=
=
=
=
=
VCC=5RB=820KohmRC=2.2Kohm =200
VBE=0.6V
-
Calculate the components in the hybrid pi model
kg
r
mSq
kTI
g
m
Cm
65.4
432507.1
==
===
pi
-
Now draw small signal equivalent circuit
Power supplies s/cat signal frequency.We are performing a superposition analysisso suppress all sourcesexcept the one we areinterested in. Voltage sources go short circuit
Coupling Capacitor
Coupling Capacitor
-
Make it look better
-
Get rid of capacitors!
Csm
Cbemo
RvgRvgv
=
=
6.94=
== CmS
oV Rg
v
vA
-
( )
CL
LCm
s
l
CLbeml
RRRR
gv
v
RRvgv
+=
=
With RL disconnected, vl=-gmRCvs
What happens if we add a load
Bias conditions unaffected
-
Csm
Cbemo
RvgRvgv
=
=
6.94=
== CmS
oV Rg
v
vA
Let RL be 10Kohm
RL
LCsm
LCbemo
RRvg
RRvgv
=
=
77=
== LCmS
oV RRg
v
vA
Gain is reduced. Loading effects of amplifiers are important as we shall see
-
Summary
We know the importance of biassing the transistor
Having biased the transistor, we need to know the gain for our signalsof interest.
Small signal model is used. It only works for small signals, as thesmall signal model assumes a straight line fit to the transistor curvesi.e it is linearised around the operating point
We have looked at small signals as applied to the basic biassing circuitand we have seen that it becomes easy to calculate the gain for small(
-
We want a better biassing technique. This is emitter biassing
What effect does RE have on the gain? A small signal circuit should help usanalyse this circuit easily.
-
Small Signal Equivalent Circuit
m
Cm
gr
qkT
Ig
pi =
=
Power supply is grounded for signals
-
We can replace the bias resistors R1 and R2 with RTH
Cbemout Rvgv =
But we need to establish vbe
We can see instantly that
This is not so obvious as REis in both the input and outputloop
-
We notice that the current through RE comprises of an element from the input circuit (ib) and gmvbe, and that the input circuit current is equivalent of vbe/rpiDefining 1/rpi as gpi ,we can see that
( )( )
( )
( ) EminCm
out
Em
inbe
EmbebeEbein
EEmbe
RggvRg
v
Rggv
v
RggvvvvvvRggv
pi
pi
pi
pi
++
=
++=
++=+=
=+
1
1
Cbemout Rvgv =As
-
EC
in
out
mEm
RR
v
v
thenggandRg
>>>> pi1
But if
( ) EminCm
out RggvRg
vpi++
=
1
Hence we do not get the gain we want (-gmRC) but a much lower gain, -RC/RE
Therefore
-
How can we get gain but use the better biasing?
Separate the DC and the AC circuit performance
Think of a way to eliminate the emitter resistor at signal frequencies
Use a capacitor in parallel to the emitter resistor!
-
Bypassed Emitter Resistor
Capacitor
-
Worked example
2kCC2
VCC=6
1k
40k
20k
CC1VIN
VOUT
CE
=100
VBE=0.7
What is the voltage gain of this circuit, with and without CE
-
First calculate IQ
( )mA14.1
1013.137.02100
=
+
==
kkII CQ
( )( ) ETH
BETHBC RR
VVII
++
==
1
2kCC2
VCC=6
1k
40k
20k
CC1VIN
VOUT
CE
=100
VBE=0.7
For the input circuit, VTH=2V and RTH=40k//20k=13.3kohm
Therefore
From
( ) VkmAVCQ 7.3214.16 ==
-
Calculate gm and Rpi
kg
r
mSq
kTIg
m
Cm
2.21046
100
4610251014.1
3
3
3
=
==
=
==
pi
( ) ( ) 94.1146.0461246
1=
++
=
++
=
kmSmSkmS
RggRg
v
v
Em
Cm
in
out
pi
With emitter resistor(no capacitor)
Low gain
-
Include CE
2kCC2
VCC=6
1k
40k
20k
CC1VIN
VOUT
CE
=100
VBE=0.7
When we include CE, we can see that intuitively REtends towards zero as the capacitor acts as a short circuit
92== Cmin
out Rgv
vTherefore
-
Common emitter amplifier
C1 and C2 are for AC coupling (DC blocking)
CE decouples the emitter (i.e low impedance to ground for AC signals)
The above are usually assumed to be open circuit for DC analysis
Small signal analysis determines gain, bandwidth etc.
-
So now we know what all the bits do!
-
Mid-band frequency response
In mid-band, gain is independent of frequency
Coupling capacitors have negligible impedance
Internal capacitances are not significant
1. Coupling and de-coupling capacitors become short circuit
2. Internal capacitances are ignored
3. DC supplies replaced with short circuits
-
Input and output impedances for a CE Amplifier
The input impedance, Rin, is the impedance seen looking into the input terminals
i.e. the ratio of input voltage to input current.
It is rpi for a CE amplifier
The output impedance, Rout, is the Norton or Thevenin impedance of the output circuit.
Using the hybrid pi model, the output circuit is a Norton equivalent (current source in parallel with a resistance). In the simplified model the current source is treated as ideal and so has infinite output impedance, thus RL is the only resistance seen.
It is RLfor a CE amplifier
-
Now lets look at the Emitter follower, or common collector
Circuit Small signal equivalent
i
Notice the introduction of r0,the output impedance of thetransistor
-
Analysis of emitter follower
Ebbb
Ebb
i
o
m
biEmbob
RiiriRii
VV
rgVriVRVgiVriV
)()(
)(,)(,
pi
pi
pipipipi
++
+=
=
+=+==
E
E
i
o
RrR
VV
)1()1(
pi ++
+=
1
)1(If
>>+
i
o
E
VV
rR pi
Ro is neglected
-
Input and output impedances
b
Ebb
b
iin i
RiriiVZ )1( pi ++==
Ein RrZ )1( pi ++=
21
21''
'
'
''
,
with parallelin is , impedance,input Actual
RRRRR
RZRZ
Z
RZZ
in
inin
inin
+=
+=
-
Input and output impedances
)1()1()1(
)1()1(
gives gRearrangin
)1()1( ,)1()1(
circuit)short (Output circuit)open (Output
pi
pi
pi
pipi
+
++
+=
++
+=
+=+=
+=+=
==
iE
Eiout
E
Eioc
ociEEoc
isc
sc
oc
o
o
out
Vr
RrRV
Z
RrRVV
r
VVRiRV
r
Vii
iV
iV
Z
pi
pi
pi
+
++=
1)1(r
RrrR
ZE
Eout
-
Summary of emitter follower Voltage gain equals 1 (if is large) Current gain is
Input impedance is large
Output impedance is small
E
E
i
o
RrR
VV
)1()1(
pi ++
+=
Ein RrZ )1( pi ++=
pi
pi
pi
+
++=
1)1(r
RrrR
ZE
Eout
-
Comparison of CC with CE
-
Things to think about
Although the basic configurations give ussome useful amplifiers, they are not ideal
Major drawbacks include Cannot accept DC signals due to coupling capacitors
Biasing resistors lead to low input impedance
-
Necessary improvements
We would like to have a high gain amplifier that can operate at DC
We would like a high input impedance to avoid loading effects
We would like to integrate these features into a single chip Big resistors dont integrate well Integrated transistors can be well matched (vital for DC systems)
This leads us to the Op-Amp
-
What do we need for an Op-Amp
Very high input impedance (virtual earth) Very low output resistance (no loading) Very high voltage gain (so we can apply feedback)
Very wide bandwidth, including DC Vout = 0 when V1=V2 irrespective of the magnitude of V1(flexible input conditions)(Equivalent of saying Vout=0 when Vin=0)
-
So whats in an Op Amp
Differential input stage Voltage gain stage Output stage
All DC coupled
-
How to operate at DC
We cant have coupling capacitors Direct coupling
We introduced these to allow biasing resistors
However, direct connection will give us biassing issues
-
Alternative way of biassing
We need to provide a finite IC We did this by pushing a known IB into the transistor
We could just pull a known current through the collector By placing a current source in the emitter
Unfortunately this stops the transistor amplifying as it now has a constant current flowing though it Transistor action requires the collector current to be varied by the transistor now not possible!
-
Think about this a bit more
A ideal current source has infinite resistance
A practical current source has a large, but finite resistance
In terms of AC (small signal), a current source will appear as this resistance
We could use this feature to make alarge resistor for AC
Therefore, care has to be taken in the assumptions made when modelling.
-
Going back to our example
In terms of gain, the CE amplifier has a value of -RC/RE
In this case RE is infinite Therefore the gain tends to zero Even if we include a non-infinite resistance, the gain is still nearly zero
If we swap RC and I over, the gain gets very large in principle (more later)
-
Lets persevere with this arrangement.as it has some advantages
We can solve this problem by introducing a second transistor in a parallel arrangement to the first
Now we have scope to allow the collector currents to vary as when one goes down, the other can go up to compensate, thus still allowing a constant IE It is constrained by the fact that the two collector currents must add up to the value of the emitter current source
-
Long tailed pair (LTP)
Current source maybe replaced by a resistor
A very useful basic amplifier stage.
The gain block used in most analogue ICs
When both inputs change levels together common mode signal
Amplifies difference between input levels
Transistors must be matched, i.e. have the same parameter values, etc.
-
Long tailed pair
The differential input voltage is given by
21 BBdin VVv =
The common mode input voltage is given by
( ) 2/21 BBcin VVV +=
If the transistors are well matched
CCCCC
ECCC
RIVV
IIII
=
===
and
221
This is the average offset voltage of the input.
From the diagram above
The effective DC inputis the VBE of each transistorwhich is the average of thetotal input.
Superimposed on top of
this is the differential input
-
Simulated responseI am sweeping V1 whilst holding V3 constant
This is the large signal response.
Notice the non-linearity.
Notice the input voltage range is low
-
Small signal analysis
rpi rpi
g vm pi1 g vm pi2
RC RC
RE
vb1 vb2vc1 vc2
ve
vvpi1 pi2
Assume that the emitter current source has a dynamic resistance of RE (could be a resistor of this value).
-
LTP analysis
222121
2121
cccout
bbcin
ccdoutbbdin
vvv
vvv
vvvvvv
+=
+=
==
For a pure differential signal, vb1 = -vb2 therefore ve=0 (half way between the 2 input potentials)
For a pure differential signal, the increase in current in Q1 equals the decrease of current in Q2. Hence, there is no change in emitter voltage, ve = 0 as no overall change in current
Thus the emitter point is at ground potential (for small signal analysis) and the two halves of the amplifier can be considered separately and RE can be ignored
rpi rpi
g vm pi1 g vm pi2
RC RC
RE
vb1 vb2vc1 vc2
ve
vvpi1 pi2
-
LTP analysis
The gain of each transistor is just -gmRC and for a pure differential signal:
dinCm
bCmbCm
ccdout
vRg
vRgvRg
vvv
=
+=
=
21
21
Thus the differential voltage gain is given by
Cmdin
doutd Rgv
vA ==
-
LTP common mode inputFor pure common mode input vb1=vb2, and by symmetry vc1=vc2.
The two transistors are in parallel and can be considered as one device with forward transconductance 2gm and input resistance rpi ( is unchanged), with the collector resistor halved as they are in parallel.
If >>1, so gm>>gpi
E
CC R
RA21
With no loss of generality we can imagine the bases and collectors joined. (No current will flow, they are at the same potential).
Hence, for pure common mode signal, the circuit behaves like a CE stage with unbypassed emitter resistor RE.
( ) EmC
m
Cin
out
Rgg
RgA
v
v
pi22122
++
==
rpi rpi
g vm pi1 g vm pi2
RC RC
RE
vb1 vb2vc1 vc2
ve
vvpi1 pi2
( )amplifier CE for the1
FromEm
inCmout Rgg
vRgv
pi++
=
-
Summary of the LTP
It provides a differential input (and output if required) with a large differential gain and small common mode gain.
If the transistors are well matched, changes in VBE due to temperature appear as a common mode voltage. Hence the amplification of thermally induced voltages is small. This makes the LTP suitable as a DC amplifier.
-
Can be implemented in 2 ways..
Ones uses NPN and the other uses PNP.
-
Both give effectively the same result
Note the difference output
is the same
So how do we generate
our current source?
-
CURRENT MIRRORS
These are useful building block circuits. The idea is that a current is supplied to the input of the mirror and an identical current flows in the output circuit, irrespective of the secondary voltage.
In an extension of this concept current mirrors may be designed that provide an output current which is a multiple of the input current. Current mirrors are useful for biassing, and creating large dynamic impedances.
The simple current mirrorini oi
Q Q1 2
Assume the transistors are identical. Since the base emitter voltages are the same
21 CC II =hence,
ino II =
-
Current mirrors
Q1 is connected as a diode
Q1 and Q2 are matched ~ almost identical device properties
is large
+
=
2iO
II
11
2 (2+)
io II
-
Several transistors may be used to give several independent current sources. Their values will be equal if the transistors are identical.
Ratios other than unity may be obtained by varying the area of the transistors.
It is the current density which is determined by VBE. Hence the current in each transistor is proportional to its area
One current mirror may have several outputs with different current ratios. Useful for setting bias currents.
ini o1i
Q Q1 2
o2i
3Q
-
Improved current mirror
1 1
2
+
++=
++=
12
12
2
i
i
I
I
( ) 12
12 ++
+=
i
o
II
+ 12 ( )
+=
+=
12
12
b
b
i
i
-
Wilson current mirror
1 1
2+
+
+
12
+
+=
+
++=
1212
2
o
i
I
I
222
2
2
++
+=
i
o
II
Improved current ratio
Improved output impedance
Q2 (diode) adds feedback
-
The Active Load
The voltage gain of a simple CE amplifier depends on the gm of the transistor and the collector load resistance.
To increase the gain it is necessary to increase gm (increase the current) or increase RC. The maximum value of the product of the collector current and the load resistance is clearly limited by the supply voltage.
One way to avoid the restriction is to use a current source, as we have seen that these have large dynamic output impedance (RC).When considering very high load resistances, we also need to remember that the collector characteristics of a CE amplifier are also that of a current source ie very high. Its value is related to the Early voltage ie the slope of the IC/VCE characteristic in the active area
The gain is given by
The maximum gain is now limited by the output resistance of the transistor.
( )ComV RrgA //=Ci
Q
Vcc
-
LTP with active loadA current mirror is often used to provide an active load for a long tailed pair, and convert the differential output to single ended.
The active load
1) increases the single ended gain for differential input
2) reduces the single ended output for common mode input (improves CMRR)
Note this is the other way up
Compares to 741. Makes overall biassing easier
The other side of the current mirroris a diode. This has a low dynamicimpedance. We cannot just use currentsources because the collector currenton one side needs to vary. Decreasing the input toQ1 results in a decrease in current through diodeQ3. This is mirrored in Q4. However Q2 is asking formore current, and the excess is forced through the load.Voltage gain is lower on the Q1/Q3side, hence the singled sided operation.
-
Gain Stage Darlington connection
By connecting the emitter of one transistor directly to the base of the next, a very high gain amplifier is created
Can be considered as 2 cascaded emitter followers with infinite emitter resistance in the first stage
1
1+
(1+)
(1+)(1+)
Current gain is effectively 2
-
Output stage
We want to minimise quiescent current We want low output resistance We need to drive useful current
-
Complementary emitter follower
(Class B output stage)
Emitter follower (common collector)has a low output impedance.
Also has a voltage gain of 1ie no gain, but has a high currentgain.
This is fine as the previous 2 stageshave given us high voltage gain.
-
Cross-over distortion
Vi must exceed +0.6V for Q1 to turn on,or be less than -0.6V for Q2 to turn on.
If an offset voltage is applied at the input, linearity is greatly improved.
-
The maximum efficiency of a class B amplifier with sine wave drive is 78.6%.
Practical class B circuit (actually class AB)
The classic circuit
Vin
Vee
RL
I1
D2
Q2
Q1
D1
Vcc
Q3
The diodes D1 and D2 provide the offset together with the current in Q3. The diodes may be diode connected transistors.
Q3 can be the gain stage.
Once again as Vin is increased,the current tries to increase. I1resists this and so VCE has to rise.The diode voltage doesnt alter, allowing low distortion operation.
-
741 op-amp
-
Simplified op-amp schematic
-
Net result:
Operation down to DC Extremely high gain (100,000 or more) Resistance to common mode signals
Makes it insensitive to temperature
0 v in gives 0 v out High input impedance, low output impedance Ideal for feedback
Feedback allows amplifier characteristics to be ignored!
-
Analogue Multiplier (2 quadrant)
One use of the LTP is as a multiplier gm is defined by the bias current and is linear
If we can modulate the bias current we can vary the gain!
-
The LTP again
dinCm
bCmbCm
ccdout
vRg
vRgvRg
vvv
=
+=
=
21
21
T
CCm V
IkTqIg ==
Let 2IC=IE (ie biassed equally)
CdinT
Eout
EC
CdinT
Cout
RVVIVII
RVVIV
22 Now ==
=
So Vout is proportional to IE x Vdin (a current multiplied by a voltage)
-
The LTP again
RVVI BEiE
=2
RVI iE 2=
So lets put a voltage to current converterin the tail. We can use a current mirror.
R
Vi2
-VEE
As it will be the current through R ifthe mirror is perfect.
We can imagine a set of conditionswhere Vi2>>VBE and so
diniout
CdinT
iout
CdinT
Eout
VVV
RVRV
VV
RVVIV
2
2
So2
So
2 Now
=
=
-
Another use
Notice that if we drive Vi2 from a variable DC source we can make a voltage controlled amplifier
Can also be used as a modulator (but only for positive signals!)
-
Limitations
Vdin has to be small due to small signal model use Vi2 can only be positive, as bias current always has to
flow
This is called a 2 quadrant multiplier:-
Vi2
Vdin
-
LTspice implementation
Varying V4 and V5.
The slope gives the gain.
Note the change in gain for changing V5 (Tail current)
The gain is the slope of thelines below.
Also note differentialsymmetry, but that the V5voltage needs to be positive to keep the tailcurrent positive
Also note non-linearity!
-
One potential use - modulator
V4 is a high frequency sine wave (Carrier)
V5 is a low frequency sine wave (Modulation)
The multiplier allows the low frequencyto be superimposed upon a carrier.
Amplitude modulation
V5 is changing thegain of the amplifiersinusoidally
-
Revisit the LTP
Remember one of its limitations is that it is only linear for small signals.
It is well known that feedback can improve linearity (Remember CE biassing?)
Can we apply feedback to our LTP to improve its linear range?
-
Emitter degeneration If we add a resistor in the emitter of our LTP we can
improves things
In this example we set the tail current to 1mA By changing the value of {Res} we can see we reduce
the gain but we increase the linear range
-
How does this work?
For the LTP, a Large signal analysis shows that (part of the assignment)
Where VID=VBE2-VBE1 Which is only linear when VID/2VT
-
Add a resistor By adding a resistor we reduce the value of VBE for a given input
voltage
VBE2 VBE1
IR IR
IRVVIRVV
IRIRVVV
DINID
IDDIN
BEBEDIN
=+=
++=
22
12
=
=
T
DIN
T
IDC V
IRVIV
VII2
2tanh2
2tanh2 00
RIV
VIRifIRVIRVV
VIRVV
IRVV
IRVIV
IRVII
MAXDIN
TDIN
TDIN
TDIN
T
DIN
T
DIN
T
DINC
0)(
00
22222
22ie
12
2if
222
22
tanh2
+
=
=
>
Which is easy to make true
(For the case of a puredifferential mode signal weneed only consider differentialchanges in VBE and IR)
To show this, noticeI=2IC and substitute in above
Maximum I occurs when
I = I0 so max VDIN= I0R
As I0R is usually bigger than 2VT
I0
-
So for our circuit If we have a maximum I of +/-0.5 mA (Half the tail current), and a
resistor of 1K then VIN can now be +/-1V for a linear response (to a first approximation)
1K
+/-1V
-
General Assignment (Bipolar design)
Analyse a 4 quadrant bipolar multiplierwhich is linear, giving +/-10V outputs for +/-5V inputs.
The coursework is in stages You will need access to LTSpice or another circuit simulator.
- Deliverables A short report (
-
Specific Tasks to be done
Perform a large signal analysis of the long tail pair and verify that
=
T
IDC V
VII2
tanh0
Relate this to the small signal analysis done in these notes and discuss the limitationsof the small signal performance ie what is the maximum signal that can be input forthe system to be linear
-
Enter and simulate the given circuit
You will have to enter a suitable simulation command, and identify theinputs and outputs
-
Analyse this and show that it is now a 4 quadrant multiplier
Verify, (and show working) that this circuit has a response of
=
T
ID
T
IDC V
VV
VII2
tanh2
tanh 210
And explain how this has removed the 2 quadrant problem.
Also say what the linear range of inputs are for this circuit.
-
You need now to extend the linear range
Show this linearises the top input by simulation
-
Include emitter degeneration in the bottom LTP
This should allow you to linearise the lower differential input across a range of your choice
-
Now adjust if necessary to meet the spec
Simulate this and calculate/choose values for voltages/currents/resistors thatshow the linear response for inputs of +/-5V with an output of +/- 10V.
There are extra marks for calculating these values instead of just trying values out
Now write a couple of paragraphs that critically evaluate the circuit
-
Assignment submission details Deadline is 8th January (first Tuesday back) Hand it in before you go if you are going to be late back
4:00 pm at the latest. ECS Coursework office. Report detailing your findings, showing the points described in previous slides.
Limit yourself to 6 pages
Web page has a summary of the assignment