Quaternion-MUSIC for vector-sensor array processing
Transcript of Quaternion-MUSIC for vector-sensor array processing
Quaternion-MUSIC for vector-sensor array
processingSebastian Miron∗, Nicolas Le Bihan† and Jerome I. Mars‡
Laboratoire des Images et des Signaux
961 rue de la Houillle Blanche, B.P. 46
38 402 Saint Martin d’Heres Cedex
FRANCE
Fax : +33 (0) 476 826 384
∗ Phone: +33 (0) 476 826 422
E-mail: [email protected]
† Phone: +33 (0) 476 826 486
E-mail: [email protected]
‡ Phone: +33 (0) 476 826 253
E-mail: [email protected]
EDICS
1-DETC : Source Detection, Localization, Classification, and Tracking
4-MDSP : MULTIDIMENSIONAL SIGNAL PROCESSING
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Quaternion-MUSIC for vector-sensor array
processing
Abstract
This paper considers the problem of direction of arrival (DOA)and polarization parameters estimation
in the case of multiple polarized sources impinging on a vector-sensor array. Quaternion model is
used and a data covariance model is proposed using quaternion formalism. Comparison between long
vector orthogonality and quaternion vector orthogonalityis also performed and its implications for
signal subspace estimation are discussed. Consequently, a MUSIC -like algorithm is presented allowing
estimation of waves DOAs and polarization parameters. The algorithm is tested in numerical simulations
and performance analysis are carried out. When compared to other MUSIC-like algorithms for vector-
sensor array, the newly proposed algorithm results in a reduction by half of memory requirements for
representation of data covariance model and reduces the computational effort, for equivalent performance.
This paper also illustrates a compact and elegant way of dealing with multicomponent complex-valued
data.
Index Terms
Vector-sensor Array, Polarization, Q-MUSIC, Quaternion Spectral Matrix (QSM), Quaternion Vector
Orthogonality, Quaternion EigenValue Decomposition (QEVD)
I. INTRODUCTION
Hamilton’s quaternionsH, as a nontrivial generalization of complex numbersC, have been considered
for a long time of pure theoretical interest. In signal processing, it is only in the last decade that quaternion-
based algorithms were proposed [1]. More recently, hypercomplex spectral transformations and color
images processing techniques have been introduced by Ell and Sangwine in [2], [3], [4], [5] and Pei in
[6]. A hypercomplex version of the multidimensional complex signals [7] was also proposed by Bulow and
Sommer [8]. In seismic data processing, as multicomponent acquisitions fit perfectly with the quaternion
model, quaternion algebra has been used to extract seismic attributes [9], [10], to enhance SNR and to
separate sources on multicomponent1 seismic dataset [11], [12]. Most of these methods encode a real-
1In this paper the termsmulticomponent data andpolarized data are used to designate the dataset recorded on a vector-sensor
array.
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valued three-component signal on the three imaginary partsof a pure quaternion (see subsection II-A). In
this paper, we propose a data model allowing to deal with multicomponent modulus-phase information
by means of quaternions. The resulting data model is then used to illustrate an eigenstructure-based
algorithm for vector-sensor array processing yielding DOA and polarization parameters estimation.
Scalar-sensor array processing algorithms and the high-resolution methods for DOA estimation are well
documented in the literature; see [13], [14], [15], [16] andreferences therein. In the last decade, as vector-
sensors became more and more reliable, polarization has been added to estimation process as an essential
attribute to characterize sources, in addition to their DOAs.Consequently, multiple authors have proposed
algorithms for multicomponent data processing. MUSIC-like methods for polarized arrays are presented
in [17], [18] and ESPRIT techniques in [19], [20], [21]. The Cramer-Rao bound for the vector-sensor case
has been studied by Weiss and Friedlander in [22] and Nehorai and Paldi in [23]. A multilinear model for
polarized seismic data and an eigenstructure-based algorithm (Vector-MUSIC) were also introduced in
[24], yielding DOA and polarization parameters (inter-sensor amplitude ratio and inter-component phase-
shift) for sources impinging on a linear, uniform array. However, these approaches assume that the data are
complex-valued, representing frequency domain samples ofthe recorded signals. Data covariance model
is then defined as the set of second-order auto-moments and cross-moments between all components of
all sensors. In this paper we propose a quaternion model for the multicomponent data that reduces by
half the memory size required for data covariance model representation resulting in a increased rapidity
of the algorithm (see sec. V). Furthermore, we show that the orthogonality constraint imposed by the
quaternion spectral matrix diagonalization is stronger that the one used for the classical spectral matrix
(see sec. III-B.2) and it provides a more accurate estimationof the signal subspace.
This paper is structured as follows. In section II, a short description of quaternions is given and
polarization model is introduced. Section III presents thequaternion spectral matrix (QSM) and discusses
quaternion-valued vectors orthogonality. A description of the new Quaternion-MUSIC (Q-MUSIC) al-
gorithm is given in section IV, and its computational complexity is compared to long-vector algorithm
complexity in section V. The performances of Q-MUSIC algorithmevaluated in simulations are described
in section VI. Finally, section VII presents the conclusions of this work.
II. QUATERNION MODEL OF A POLARIZED SOURCE
A. Quaternions
Quaternions are a four dimensional hypercomplex numbers system. Discovered by Sir R.W. Hamilton
in 1843 [25], they are an extension of complex numbers to 4D space. A quaternionq is described by
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four components (one real and three imaginaries). It can be expressed in its Cartesian form as:
q = a + ib + jc + kd, (1)
where:
i2 = j2 = k2 = ijk = −1,
ij = k ji = −k,ki = j ik = −j,jk = i kj = −i.
Many books discuss about quaternions and their properties.Basics about hypercomplex numbers
systems can be found in [26], while a thorough review about quaternions can be found in Ward’s book
[27].
Several properties of complex numbers can be extended to quaternions. Some of them are given below:
- the conjugate ofq, notedq, is given by:q = a − ib − jc − kd;
- a pure quaternion is a quaternion which real part is null:q = ib + jc + kd;
- the modulus of a quaternionq is |q| =√
qq =√
qq =√
a2 + b2 + c2 + d2 and its inverse is given
by
q−1 =q
|q|2 ; (2)
- a quaternion is said to benull iff a = b = c = d = 0;
- the set of quaternions, denoted byH, forms a non-commutative normed division algebra, that means
that given two quaternionsq1 andq2 :
q1q2 6= q2q1; (3)
- conjugation overH is an anti-involution:
q1q2 = q2 q1. (4)
It is well known [28] that a quaternion is uniquely expressed as: q = q (1) +jq(2), whereq(1) = a+ib
and q(2) = c − id. This is known as the Cayley-Dickson form. It is also possible toexpressq in an
alternate Cayley-Dickson form. Thus, any quaternionq can be written as:
q = q′ + iq′′, (5)
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whereq′ = a + jc andq′′ = b + jd. This notation will be used in the polarized signal quaternion model
proposed in the following section.
B. Polarization model
Consider a scenario with one polarized source, assumed to be a centered, stationary stochastic process,
emitting a wavefield in an isotropic, homogeneous medium. This wavefield is recorded on a two-
component noise-free sensor, resulting in two highly correlated temporal seriess 1[tn], s2[tn] ∈ RNt .
After performing a discrete Fourier transform along time dimension on each of the two components, the
expression for the two components in frequency domain becomes:
x1[νm] = β1[νm]ejα1[νm] and x2[νm] = β2[νm]ejα2[νm], (6)
wherex1, x2 ∈ CNν , νm is the discrete Fourier frequency,β1, β2 andα1, α2 are the amplitudes and
phases of the two components of the signal at the given frequency νm.
Using the imaginary operatorj instead ofi as Fourier transformation axis, does not alter the physical
meaning of Fourier phase and modulus. To simplify the notation, we shall ignore the frequency argument
in these expressions and consider working at a given frequency ν m = νm0. As we do not have access
to the exact amplitude and the initial phase of the source, first component is considered as reference
and relative phase and amplitude are estimated. The statistical relationship between components can be
expressed as a constant complex ratio betweenx 1 and x2 or as a constant modulus ratioβ2/β1 = ρ
and a constant phase-shiftϕ = α2 − α1. These two parametersρ andϕ must be estimated in order to
describe the polarization ellipse orientation and eccentricity [29].
Using notations given in equation (6), we construct the quaternion signalx ∈ H, describing a 2C
signal on one sensor:
x = β1ejα1 + iβ2e
jα2 , (7)
where:
ejα1 = cos α1 + j sinα1
ejα2 = cos α2 + j sinα2
. (8)
Expression (7) can be written in extended form as:
x = β1 cos α1 + iβ2 cos α2 + jβ1 sin α1 + kβ2 sin α2. (9)
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By this way, a new transformation is defined mapping the two-component complex-valued signal space
to the quaternion-valued signal space. This transformation maps the even parts of the 2C signal on scalar
and i imaginary fields of a quaternion while the odd parts are mappedto the two others remaining
imaginary fields (jandk).
Replacingβ2 andα2 in (7) by:
β2 = ρβ1
α2 = ϕ + α1
, (10)
observationx is written as the product between a quaternionic expressionp(ρ, ϕ) describing the
polarized wave behavior on the two components (ρ is the amplitude ratio andϕ is the phase-shift)
and the complex amplitude of this wave on the first component:
x = p(ρ, ϕ)β1ejα1 , (11)
where:
p(ρ, ϕ) = 1 + iρejϕ. (12)
In order to extend this model to the multi-sensor case and to introduce the new Q-MUSIC algorithm,
we consider a linear, uniform vector-sensor array ofN sensors (fig.1). Assume that far-field waves from
K sources (K-known, K < N ) impinge on this antenna. Sources are supposed to be decorrelated,
spatially coherent and confined in the array plane. Their polarizations are also stationary in time and
space (distance). Noise is spatially white and not polarized2.
To describe wavefield propagation along the array, it is necessary to model a time delay between
sensors. In the far-field hypothesis, this delay is simply described as an inter-sensor phase-shiftθ. The
source direction of arrival (DOA)α, can then be calculated using the following formula:
θ = 2πν∆x sin α
v, (13)
where ∆x is the inter-sensors distance,v is the wave propagation velocity andν is the working
frequency. Taking the first sensor (on the antenna) as reference,k th source propagation along the antenna
is described by a vectorak ∈ CN :
2Consider a two-components centered noiseb(m) = [b1(m), b2(m)]T recorded on a single vector-sensor, whereb1(m), b2(m)
are Gaussian noise with variancesσ1, σ2. Such a noise isnot polarized if its covariance matrixξbbH = diag(σ1, σ2).
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ak(θk) =[1, e−jθk , . . . , e−j(N−1)θk
]T. (14)
Thus, the output of the vector-sensor array is given by a column quaternion vectorx ∈ HN , equal to
the sum of theK sources contributions (added with a noise term):
x =K∑
k=1
dkβ1k exp(jα1k) + n. (15)
In (15), n ∈ HN contains noise contribution on all sensors and components,β1k et α1k are given by
(7) anddk ∈ HN is a quaternion vector describingk th source behavior on the vector-sensor array as:
dk(θk, ρk, ϕk) = pk(ρk, ϕk)ak(θk), (16)
thus:
dk(θk, ρk, ϕk) =[1 + iρke
jϕk , e−jθk + iρkej(ϕk−θk), . . . , e−j(N−1)θk + iρke
j(ϕk−(N−1)θk)]T
. (17)
An unitary quaternion vector can be obtained dividingdk by its norm3. Thereafter,ck will refer to
the unitary vectorck = dk
‖dk‖and‖dk‖ =
√N(1 + ρ2
k) to its norm.
III. QUATERNION SPECTRAL MATRIX
This section introduces a novel data covariance model for the polarization model presented in section
II.
A. Quaternion spectral matrix
For scalar-sensor arrays, the spectral matrix ([30], [31])is given by the set of second order auto-
moments and cross-moments of all sensors on the antenna. We introduce the equivalent second order
representation for a vector-sensor array using quaternionformalism. Quaternion spectral matrix (QSM)
Ω ∈ HN×N is defined as:
Ω = Exx/, (18)
3The norm of a quaternion vectorq is defined as‖q‖ =√
q/q, where/ represents the quaternionic transposition-conjugation
operator.
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where E. is the mathematical expectation operator andx ∈ HN is the quaternionic observation
vector introduced in (15). If we replace (15) in (18) and usingrelation (4),Ω can be written as:
Ω = E
(K∑
k=1
ck‖dk‖β1k exp(jα1k) + n
)(K∑
k=1
ck‖dk‖β1k exp(jα1k) + n
)/
= E
(K∑
k=1
ck‖dk‖β1k exp(jα1k) + n
)(K∑
k=1
β1k exp(−jα1k)c/k‖dk‖ + n/
). (19)
Assuming the decorrelation between the noise and the sources and between sources themselves, the
expression of the quaternion spectral matrix becomes:
Ω = ΩS + ΩN , (20)
where
ΩS =
K∑
k=1
σ2kckc
/k, (21)
andΩN = Enn/ is a matrix containing noise second order statistics. In (20), ΩS is the signal part
of QSM andσ2k = (β1k‖dk‖)2 = N(β2
1k + β22k) representskth source power on the antenna.
In order to understand the statistical meaning of QSM, the links between quaternions and complex
numbers statistics must be studied. So, the output of the vector-sensor arrayx ∈ HN can be written
according to the complex-valued outputsx1,x2 ∈ CN of the two components of the array as:
x = x1 + ix2. (22)
Introducing (22) in (18), the representation ofΩ becomes:
Ω = Ex1xH1 + Ex1x
H2 i+ i Ex2x
H1 + i Ex2x
H2 i, (23)
with H the complex transposition-conjugation operator. When considering (23) the reader must keep
in mind that x1,x2 are j-complex vectors and multiplication byi of a j-complex number is not
commutative. One can identify in (23) the expressions of auto-covariance and cross-covariance matrices
for the two components of the vector array, meaning that QSM contains intrinsically all the second-order
information available on the antenna. The fact that none of these matrices is explicitly calculated when
estimating QSM, reduces the computational time of the algorithm and saves memory.
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Property: The noise-free part of QSM, ΩS is a Toeplitz matrix.
Proof: Consider the signal part ofΩ:
ΩS =K∑
k=1
σ2kckc
/k, (24)
where ck is given by (16). Thus, introducing (16) in (24) and using quaternion product conjugate
expression:
ΩS =
K∑
k=1
σ2kpkaka
Hk pk =
K∑
k=1
σ2kpkAkpk, (25)
in which pk ∈ H is given by (12) andAk = akaHk is a complex-hermitian matrix (Ak ∈ C
N×N )
presenting a Toeplitz form:
Ak =
1 ejθk . . .
e−jθk 1 ejθk
... e−jθk. ..
1
. (26)
Multiplication of Ak on the left bypk and on the right bypk conserves the Toeplitz structure:Ck =
pkAkpk. Thus,ΩS can be written as a weighted sum of quaternion Toeplitz matrices: ΩS =∑K
k=1 σ2kCk.
As the noise component of the signal (see eq. (15)) is assumed spatially white and non-polarized, the
noise part of QSM,ΩN = ξnn/, is a real diagonal matrix for which the diagonal entries represent the
noise power on theN sensors.
B. Subspace method
Eigenstructure methods are based on the decomposition of the vector space spanned by the observation
vectorx in orthogonal subspaces using an energy criteria.
1) Quaternion EigenValue Decomposition (QEVD): Researchers in areas such as quantum mechanics
[32], vector-signal processing [11], [12] and color image processing [33] took interest recently in compu-
tation of Eigenvalue Decomposition (EVD) and the Singular Value Decomposition (SVD) of quaternion
matrices. Due to the noncommutativity of quaternions, thereare two types (rightand left) of quaternion
eigenvalues. Theory about the right quaternionic eigenvalues is well established [28], [34]. However this
is not the case for the left eigenvalues of quaternion matrices, as their existence is still problematic [35].
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Therefore, in this paper, the termsquaternion eigenvalues andquaternion eigenvectors are used forright
eigenvalues andright eigenvectors.
In practice, we have only access to an estimation of the quaternion spectral matrixΩ (obtained by
classical statistical average or some other averaging technique). By construction, QSM is quaternion
hermitian, Ω/ = Ω. It can be shown that the eigenvalues for a quaternion hermitian matrix are real-
valued (see [36]). Quaternion spectral matrix can thus be written as:
Ω =
N∑
k=1
λkuku/k, (27)
whereλk are the real eigenvalues anduk are theN orthonormal quaternion-valued eigenvectors.
2) Quaternion vectors orthogonality: In order to define orthogonality for quaternion-valued vectors,
we have to generalize the definition ofscalar product to the quaternionic case. For two quaternion-valued
column vectorsw,y ∈ HN , the scalar product is defined as:
< w,y >H= y/w. (28)
We say that two quaternion vectors areorthogonal if their scalar product is null. Thus, theu k
vectors in (27) form a quaternionic orthonormal basis in theobservation space spanned byx. To better
understand how quaternionic orthogonality works, consider two quaternion-valued vectorsw,y ∈ HN ,
having Cayley-Dickson representations such as:
w = w1 + iw2
y = y1 + iy2
. (29)
In (29),w1,w2,y1,y2 ∈ CN are complex-valued vectors that can be assimilated to the components of
a 2C vector-sensor array (see eq. (22)). If the two components are processed separately as scalar datasets
(as in the case of MUSIC for scalar-sensor array), the orthogonality relationships for the vectors of the
orthogonal basis can be written as:
yH1 w1 = 0
yH2 w2 = 0
. (30)
The classical subspace methods in vector-sensor array processing uselong-vector orthogonality, which
is in fact the orthogonality for the complex vectorsw, y ∈ C2N obtained by concatenating the two
components:
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w =
w1
w2
andy =
y1
y2
. (31)
In the first case, the quaternionic orthogonality implies< w,y >H= 0, while in the long-vector case,
complex vectors orthogonality implies:< w, y >C= 0. From (28), (29), orthogonality between the two
vectors of quaternions is equivalent to:
(yH1 − yH
2 i)(w1 + iw2) = 0, (32)
which leads to the two equalities:
yH1 w1 + yH
2 w2 = 0 (33)
and
yT1 w2 = yT
2 w1. (34)
Similarly, using the long-vector representations (31), complex orthogonality leads to:
[yH1 yH
2 ]
w1
w2
= 0, (35)
which is equivalent to (33).
It must be noticed that quaternion orthogonality induces one more constraint (eq. (34)) on the rela-
tionship between the two components than does the complex orthogonality. The question is whether the
second constraint is incompatible with the first one ((33) excludes (34)) or it is trivial ((33) implies (34)).
Two numerical examples are given to answer these questions.
Exemple 1 Considerw1,w2,y1,y2 ∈ C3 given by:
w1 =
−0.3286 − 0.1998j
−0.3090 − 0.2856j
−0.3368 − 0.3534j
, w2 =
−0.3529 − 0.3546j
−0.3103 − 0.1448j
−0.0791 − 0.2511j
,
y1 =
0.1232 − 0.2396j
0.0425 − 0.3371j
0.0709 + 0.4814j
, y2 =
0.0804 + 0.1064j
−0.2400 + 0.3502j
0.0869 − 0.6080j
.
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For this set of complex vectors, both relations (33) and (34)are fulfilled, proving the existence of
quaternionic orthogonality and implying the compatibility of the two constraints.
Exemple 2 A second example is considered with the following numerical values:
w1 =
−0.2918 − 0.2407j
−0.2933 − 0.2334j
−0.2549 − 0.2104j
, w2 =
−0.3124 − 0.2973j
−0.4091 − 0.3374j
−0.3130 − 0.2048j
,
y1 =
0.3896 + 0.3205j
−0.4620 + 0.2509j
0.3200 − 0.2827j
, y2 =
−0.2953 − 0.1160j
−0.0177 + 0.1209j
0.1220 − 0.3954j
.
By calculation, it can be shown that in this case (33) is verified while (34) is not, meaning that the
second constraint is not trivial. These vectors arecomplex orthogonal (long vector) but they are not
quaternion orthogonal. This signifies that quaternion orthogonality is a ”stronger” constraint:
< w,y >H= 0 ⇒ < w, y >C= 0. (36)
The reciprocal expression is not always true.
We show under which conditions long vector orthogonality andquaternion orthogonality are equivalent.
Assimilatingw1,w2 andy1,y2 to the components of two polarized sources on a 2C sensor array, the
following relations can be written:
w2 = w1ρwejϕw
y2 = y1ρyejϕy
, (37)
whereρw, ϕw andρy, ϕy are the polarization parameters of the sources (see (12)). Replacing (37) in
(34) leads to:
yT1 w1ρwejϕw = yT
1 w1ρyejϕy . (38)
By imposing this relation to be true for anyw1,y1 ∈ CN , we getρw = ρy andϕw = ϕy, meaning
that sources polarizations are identical. Thus, theoretically (if we don’t take into account the statistical
aspect in the covariance matrix) the vector basis obtained by imposing quaternion orthogonality or long
vector orthogonality are identical only if sources contained in the signal part have identical polarizations
or if there is only one source present in the signal. Otherwise,these two methods yield different results.
Equations (30), (33) and (34), can be rewritten using the complex scalar product as:
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< w1,y1 >C= 0
< w2,y2 >C= 0, (39)
< w1,y1 >C = − < w2,y2 >C , (40)
< w1,y∗2 >C = < w2,y
∗1 >C , (41)
where∗ represents the complex conjugate of a vector. Tables I and IIsummarize the discussion on vector
orthogonality in terms of scalar product between the components. Each cell of the tables corresponds to
the scalar product of the associated complex vectors.
< ., . > y1 y2
w1 0
w2 0
TABLE I
RELATIONSHIPS BETWEEN THE COMPONENTS WHEN PROCESSING EACH COMPONENT SEPARATELY
< ., . > y1 y2 y∗
1 y∗
2
w1 ⇒ →w2 ⇐ →
⇒ , ⇐ : long vector orthogonality constraint
⇒ , ⇐ , → : quaternion vector orthogonality constraint
TABLE II
RELATIONSHIPS BETWEEN THE COMPONENTS FOR LONG VECTOR AND QUATERNION ORTHOGONALITY
The identical shaped arrows indicate which scalar products are forced to be equal (in absolute value).
The direction of the arrow designates the sign (right arrow for positive and left arrow for negative) of
the product in relationship with the corresponding equal quantity. The double arrows represent the long
vector constraint and an empty cell indicates that there is no constraint between the considered vectors.
When processing one component at a time (table I), one can seethat there are no links between the
scalar products of the components. Each couple of components is forced to orthogonality independently,
representing two different self-sufficient estimation problems. The long vector orthogonality imposes
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a constraint between the corresponding components of the vectors (see table II - the double arrows)
((w1,y1) and (w2,y2)) and the quaternion orthogonality restrains even more the freedom of the com-
ponents forcing an additional cross-component relationship (table II - the simple arrows).
An evident question arising after this discussion on orthogonality is what would be the effect of this
stronger orthogonality constraint on subspace-based algorithms. We show in the next part that for a two-
component complex-valued dataset, quaternion vector orthogonality provides a more accurate estimation
of the signal subspace than the long vector orthogonality constraint.
Consider two square complex-valued matricesC1,C2 ∈ C20×20, whose entries are generated using a
random uniform number generator.C1 andC2 could be assimilated to datasets (in the frequency domain)
recorded on a two-component array of 20 sensors. Starting from these two matrices, we create along
vector complex matrixClv ∈ C40×20 by concatenation ofC1,C2:
Clv =
C1
C2
(42)
and aquaternion matrix Cq ∈ H20×20 as:
Cq = C1 + iC2. (43)
After performing the singular value decomposition (SVD) ofClv and the quaternion singular value
decomposition (QSVD) ofCq, the matrices can be written as a sum of 20 rank-1 terms:
Clv =
20∑
k=1
ukσkvHk , where uk ∈ C
40,vk ∈ C20 (44)
Cq =
20∑
k=1
pkδkq/k, where pk,qk ∈ H
20. (45)
The uk complex-valued vectors in (44) and the quaternion vectorspk in (45) form a long vector and
a quaternion orthogonal basis respectively in the vector space defined by the two components. Rank-R
approximations ofClv andCq are constructed as:
CRlv =
R∑
k=1
ukσkvHk , (46)
CRq =
R∑
k=1
pkδkq/k, (47)
with 1 ≤ R ≤ 20.
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In order to estimate the rank-R approximation error for the long vector and quaternionic decompositions,
the two following error functions are computed:
Elv(R) =‖Clv − CR
lv‖‖C1‖ + ‖C2‖
, (48)
Eq(R) =‖Cq −CR
q ‖‖C1‖ + ‖C2‖
, (49)
where‖.‖ is the Frobenius norm4 of a complex or quaternion matrix.
Fig. 2 plotsElv andEq versus the approximation rankR. These two curves are obtained by averaging
the error functions computed for 100 independent realizations ofC 1, C2. One can see that for a rank-1
approximation, the long vector and the quaternion approaches yield the same estimation error. This is a
confirmation of the theoretical result (that we saw earlier inthis section) stating that in the case of one
source present in the signal (or if sources have identical polarizations) the two kinds of orthogonality are
equivalent. For all the other ranks, the approximation error obtained using the quaternionic approach is
smaller than the long vector one (Eq(R) < Elv(R), 1 < R < 20).
In conclusion we can state that the use of quaternion vector orthogonality to estimate the signal
subspace on a two component vector-sensor array improves estimation accuracy, compared to the long
vector method. The explanation is that the energy of the signals on a 2C section can be more precisely
concentrated on a quaternion vector orthogonal basis than on a long vector one.
IV. QUATERNION-MUSIC ESTIMATOR
Using the data covariance model illustrated in section III, wepropose a MUSIC-like algorithm allowing
estimation of DOA (by inter-sensor phase-shiftθ) and polarization parametersρ, ϕ (see eqs. (16), (17)).
By identification of (20) with (27), we associate the firstK eigenvalues to the signal part of the observation
and the rest ofN−K to the noise part. The choice ofK is made by studying the gaps in the quaternionic
eigenvalues curve. Statistical criteria such as the Akaike information criterion (AIC) [37] and the minimum
description length (MDL) [38] can also be applied but they arelittle robust when noise is considered.
In the sequel, we consider thatK is priory known and encourage the interested reader to examine
the bibliographic references given here. The quaternion eigenvectors in (27) associated to the firstK
4The Frobenius norm of aM × N matrix A is defined as the square root of the sum of the squared norm of its elements
‖A‖ =
M
m=1
N
n=1 |anm|2.
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IEEE TRANSACTIONS ON SIGNAL PROCESSING 15
eigenvalues span the signal vector subspace and the otherN −K, the noise part of the observation vector
space. Thus, the projector on the noise subspace is defined as:
ΠN =N∑
k=K+1
uku/k. (50)
The quaternion steering-vectorq ∈ HN is then generated:
q(θ, ρ, ϕ) =√
N(1 + ρ2)
1 + iρejϕ
e−jθ + iρej(ϕ−θ)
...
e−j(N−1)θ + iρej(ϕ−(N−1)θ)
. (51)
q is a three-parameters unitary vector, modeling the arrivalof a source of DOAθ and polarization
parametersρ andϕ on a 2C sensor array. Quaternion-MUSIC estimator (Q-MUSIC) is then computed
by projecting the steering-vectorq(θ, ρ, ϕ) on the noise subspace:
MQ(θ, ρ, ϕ) =1
‖ΠN q(θ, ρ, ϕ)‖ , (52)
where‖.‖ is the norm of a quaternion vector. The functional in (52) hasmaxima for sets of (θ, ρ, ϕ)
corresponding to sources present in the signal. By varyingθ, ρ, ϕ within a given domain with a chosen
step, a three dimensional surface is computed. The estimated values ofθ, ρ andϕ are the coordinates of
the most important local maxima on this surface. Assuming that the iteration step is sufficiently small for
a correct sampling of the hyper-surface, the search for local maxima is automatically done by comparing
each point on this surface with its neighbors. The firstK maxima correspond to theK sources present
in the signal. This way, the estimation process ofθ, ρ andϕ is quasi-unsupervised.
V. COMPUTATIONAL ISSUES
This section addresses the problem of computational complexity for long vector and quaternion algo-
rithms. A full estimation of the computational complexity of the methods is difficult and is little relevant
as it is hardware and software dependent. In the sequel we onlyfocus on one aspect of the algorithm:
the estimation of the covariance matrix. This procedure, asit implies repetitive operations, best illustrates
the complexity difference between the two algorithms. The complexity of the methods are evaluated in
terms of memory requirements, memory traffic and basic arithmetical operations: real numbers addition
(A), multiplication (M) and division (D).
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Let us consider a vector-sensor array composed ofN two-component sensors. In frequency domain, a
snapshot of the array is given by two complex-valued vectorsw 1,w2 ∈ CN . The quaternion representation
w ∈ HN and the long-vector representationw ∈ C
2N of the observation vector have the expressions given
by (29) and (31). The corresponding covariance matrices areas it follows:Ω = Eww / ∈ HN×N and
Ω = EwwH ∈ C2N×2N . If averaging overΛ particular realizations of the covariance matrix is used for
estimation, we can writeΩ = 1Λ
∑Λλ=1 wλw
/λ = 1
Λ
∑Λλ=1 Ωλ and Ω = 1
Λ
∑Λλ=1 wλw
Hλ = 1
Λ
∑Λλ=1 Ωλ.
Each one of theΩλ matrices hasN 2 quaternionic entries and can be represented at machine memory
level on4N 2 real fields, while theΩλ matrices have4N 2 complex entries each, corresponding to8N 2
real values. This way, quaternion algorithm reduces by halfthe memory requirements for representation
of data covariance model, resulting also in a total diminution by a factor of≈ 2 of memory traffic
operations (data retrieving and writing) and a proportionalgain in speed.
Let us evaluate now the total number of basic arithmetical operations needed for covariance matrix
estimation. Each of the quaternion entries ofΩλ is the result of the multiplication of two quaternions.
Multiplication of two quaternions implies 16 real multiplications (M) and 12 real additions (A), that is a
total of 16N2 (M) and 12N 2 (A) for the whole matrix. For the complex matrixΩλ we have16N 2 (M)
and8N 2 (A). Thus, the summation∑Λ
λ=1 Ωλ needs a total of16N 2Λ (M) and12N 2Λ+(Λ− 1)4N 2 =
16N2Λ− 4N2 (A) while∑Λ
λ=1 Ωλ requires16N 2Λ (M) and8N 2Λ+(Λ− 1)8N 2 = 16N2Λ− 8N2(A).
These results take into account the observation vectors multiplications as well as matrix additions. The
final division byΛ means another4N 2 real numbers divisions (D) for the quaternion algorithm and8N 2
(D) for the long-vector one. Table III recapitulates the covariance matrix computational effort for the two
algorithms.
Memory requirements Memory operations Real multiplications Real additions Real divisions
(real values) (M) (A) (D)
QSM 4N2 ≈ 4N2Λ 16N2Λ 16N2Λ − 4N2 4N2
Long-vector SM 8N2 ≈ 8N2Λ 16N2Λ 16N2Λ − 8N2 8N2
TABLE III
COMPUTATIONAL EFFORT FOR COVARIANCE MATRIX ESTIMATION
As we can see in table III, the quaternion algorithm reduces thememory requirements for data
covariance model representation by a factor of two. Consequently the memory traffic if reduced by
approximately the same factor, resulting in an important gain in rapidity, especially for large data size.
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Regarding the number of elementary operations on real values, the quaternionic approach demands4N 2
additions moreover and4N 2 divisions less than the long-vector method. The computational complexity
for division is several times more important than for addition, implying higher computational cost for
long-vector.
The computation of the quaternionic eigenvectors of the estimated matrixΩ ∈ HN×N can be performed
using algorithms dealing with complex numbers or quaternions. The methods based on complex numbers
come down to diagonalizing the complex adjoint matrix ofΩ, that is a complex-valued matrix of size
2N ×2N (see [28], [34]). In this case, the computational complexity of the eigenvalue decomposition of
the quaternionic matrixΩ is equivalent to the decomposition complexity of the complex matrix Ω. The
advantage of this approach is the possibility of using complex matrix diagonalization routines already
existing in the literature (ex. LAPACK), that are computationally optimized.
Nevertheless, it was shown (see [39]) that working directly inquaternionic domain improves the
convergence speed of the algorithms compared to complex approach. This reinforces the idea that the
use of quaternions can enhance the performance of algorithms.
Generally, the use of quaternions in algorithms reduces the computational effort, due to the compact
handling of the data.
VI. SIMULATION RESULTS
The performances of Q-MUSIC estimator are compared to its scalar version [13] and to Vector-MUSIC
(V-MUSIC) [24] for vector-sensor array processing. For the multicomponent algorithms (Q-MUSIC and
V-MUSIC), three-dimensional surfaces (functions of parameters θ, ρ, ϕ ) are computed. The presented
figures are cuts of this hyper-surfaces for fixed values of oneor two parameters.
First, we consider a scenario with one polarized source impinging on a 2C-sensor array composed of
10 identical equally-spaced sensors. The source has the DOAθ = 0.93 rad, polarization parameters:
ρ = 3 , ϕ = 0.27 rad and random initial phase. Gaussian noise has been added to this signal up to a
SNR5 of 0 dB. A computation step of0.001 rad has been used forθ and0.05 for ρ andϕ.
In figure 3 we have represented the DOA (inter-sensors phase-shift) estimation for the proposed
algorithm compared to V-MUSIC and its scalar version, in three different runs for different numbers
of snapshots. The curves have been plotted forρ = 3 andϕ = 0.27 rad (the polarization parameters of
5If Sc
k(ν) and Nc
k(ν) are the frequency values for the signal and noise part of the signal on thekth sensor of thecth
component, the signal to noise ratio for a 2C dataset recorded on K sensors is defined asSNR(ν0) = 2
c=1 Kk=1
(Skn(ν0))2
2
c=1 Kk=1
(Nkn(ν0))2
for the working frequencyν0.
February 23, 2005 DRAFT
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the source). The performance of the new algorithm is comparable to Vector-MUSIC as one can see in
fig.3 (a,b,c). For a large number of samples (a good covariance estimation) (fig.3.a), the 3dB detection
lobe width for Q-MUSIC is even narrower compared to the other vectorial algorithm. This means that for
an accurate estimation of QSM, the quaternion algorithm yields better resolution power than V-MUSIC.
Fig. 3 shows also that multicomponent information improves considerably the detection resolution; for a
poor number of samples scalar detection fails badly (fig.3.c).Fig. 4 (a,b) plots the detection curves for
polarization parameters (ρ andϕ) computed by the multicomponent algorithms. This time a computation
step of0.02 was used forρ andϕ, in order to improve resolution.
Figure 4 (a,b) also shows that for a one source scenario, the Q-MUSIC estimation of polarization
parameters is equivalent (and sometimes even more resolutive) to Vector-MUSIC algorithm.
Next we study the case of two equally powered sources, under the same assumptions. The simulated
parameters for the impinging waves areθ1 = 0.48 rad, ρ1 = 2.5, ϕ1 = −0.18 rad andθ2 = −0.25 rad,
ρ2 = 3, ϕ2 = 0.15 rad. In fig. 5.a the values of the two three-parameters surfaces, Q-MUSIC and
V-MUSIC, are plotted for two fixed values corresponding to polarization parameters of the first source
(ρ1 = 2.5, ϕ1 = −0.18 rad). One can observe that both algorithms present an expected strong answer
for the DOA of the first source (θ1 = 0.48 rad) and a residual answer forθ2 = −0.25 rad corresponding
to second source. This residual answer is due to incomplete decorrelation of the two sources. The main
detection lobes for Q-MUSIC and V-MUSIC are completely superposed, while the secondary one is
slightly stronger for the quaternion method. The explanation is the reduction of data covariance space
dimension for Q-MUSIC algorithm (see section I), resulting ina more important sensitivity of the
algorithm to sources correlation. The same phenomenon can be observed for the second source (fig.
5.b); this time the curves were plotted for two fixed values corresponding to second source polarization
parameters.
The polarization parameters plan corresponding to the firstsource (θ 1 = 0.48 rad) is represented for
Vector-MUSIC estimator in fig. 6.a and for Q-MUSIC in fig. 6.b. In thestudied case, both algorithms
perform a correct detection, the difference is that detection lobe (cone) is slightly wider for the quater-
nionic version of the method (fig. 6.b) compared to Vector-MUSIC. The situation is similar for the second
source polarization parameters. This widening in the polarization domain can be explained by the fact
that data covariance compression is performed along the polarization dimension of the dataset.
Thus, even in a multiple emitter scenario, the proposed algorithm yields performances comparable to
similar techniques (Vector-MUSIC), using less computational resources.
In order to have a statistical characterization of Q-MUSIC estimator, its performance is compared
February 23, 2005 DRAFT
IEEE TRANSACTIONS ON SIGNAL PROCESSING 19
to Vector-MUSIC and Scalar-MUSIC estimators in Monte Carlo runs. Two equal-power uncorrelated
polarized sources, with random initial phases, impinge on a two-component sensor-array composed of 10
equally-spaced sensors. The sources DOAs areθ 1 = −0.7 rad, θ2 = 0.5 rad and they have the following
polarization parameters:ρ1 = 2.5, ϕ1 = −0.18 rad, ρ2 = 3, ϕ2 = 0.15 rad. Figure 7 plots the DOA root-
mean-square (RMS) estimation error for the estimators mentioned bellow. One hundred snapshots are used
in each Monte Carlo run. Three hundred independent runs contribute to each number in the figure. Additive
white gaussian noise is present in different signal to noise proportions. The RMS error ofθ is defined as
the root-mean-square of the RMS estimation error ofθ1 and θ2
(RMS(θ) =
√RMS2(
θ1)+RMS2(
θ2)2
).
For Scalar-MUSIC a mean is operated over the two components.
Fig 7 shows that the two algorithms, Q-MUSIC and V-MUSIC, present equivalent performance, their
RMS error curves are almost totally superposed. Nevertheless, their estimation error is clearly inferior to
scalar version of the algorithm.
VII. C ONCLUSIONS
In this paper we have illustrated a compact and elegant way of dealing with two-component complex-
valued datasets in vector-sensor array processing, using quaternions. A new data model and data co-
variance model (QSM) was proposed and a new direction-findingmethod (Q-MUSIC) exploiting spatial
and polarization diversity was introduced. This algorithmallows DOA and polarization estimation for
multiple sources on a vector-sensor array.
We showed that the quaternion vector orthogonality allows a more accurate estimation of the noise
subspace for a two component dataset, compensating for the lost of performance due to the reduction of
data covariance representation (QSM) size.
The proposed method has been compared to the classical MUSIC algorithm for scalar-sensor array and
to another MUSIC-like algorithm for vector-sensor array processing. Q-MUSIC is clearly more accurate
than classical (scalar) MUSIC and yields equivalent resultscompared to Vector-MUSIC algorithm,
reducing the computational burden and dividing by half the memory space required. The method has
a better resolution power for an accurate estimation of the QSM, but it is more sensitive to sources
correlation than Vector-MUSIC algorithm. An extended analysis of Q-MUSIC behavior (Cramer-Rao
bound, robustness to colored or correlated noise, etc.) is beyond the scope of this paper and should be
included in a subsequent article.
The presented results emphasize the potential of quaternions to model polarized signals and put into
perspective the possibility of describing signals having more than two complex-valued components using
February 23, 2005 DRAFT
IEEE TRANSACTIONS ON SIGNAL PROCESSING 20
higher dimensional hypercomplex algebras.
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x∆
α
N
two componentsensor
x2
x1
x2 x2
x1 x1
Fig. 1. Acquisition scheme
0 2 4 6 8 10 12 14 16 18 200
0.05
0.1
0.15
0.2
0.25
0.3
0.35
0.4
0.45
0.5
Rank (R)
App
roxi
mat
ion
erro
r
long vector approach (Elv
)
quaternionic approach (Eq)
Fig. 2. Rank approximation error for the long vector and quaternionic approaches
February 23, 2005 DRAFT
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0.5 0.6 0.7 0.8 0.9 1 1.1 1.2 1.3
5
10
15
20
25
30
35
40
Vector−MUSICQ−MUSICScalar−MUSIC
source DOA
0.5 0.6 0.7 0.8 0.9 1 1.1 1.2 1.31
2
3
4
5
6
7
8
9
10
11
12
Vector−MUSICQ−MUSICScalar−MUSIC source DOA
0.5 0.6 0.7 0.8 0.9 1 1.1 1.2 1.31
1.2
1.4
1.6
1.8
2
2.2
2.4
2.6
2.8
3Vector−MUSICQ−MUSICScalar−MUSIC
source DOA
DOA by θ DOA by θ DOA by θ
(a) 1000 samples (b) 100 samples (c) 10 samples
Fig. 3. Q-MUSIC, Vector-MUSIC and Scalar-MUSIC in three runs for different numbers of samples
2.6 2.7 2.8 2.9 3 3.1 3.2 3.3 3.415
20
25
30
35
40
45
50
Q−MUSICVector−MUSIC
Theoretical Value
−0.1 0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8
5
10
15
20
25
30
35
40
45
50
Q−MUSICVector−MUSIC
Theoretical Value
ρ ϕ (rad)
(for θ = 0.93 rad andϕ = 0.27 rad) (for θ = 0.93 rad andρ = 3)
(a) (b)
Fig. 4. Q-MUSIC and Vector-MUSIC estimation forρ andϕ for 1000 snapshots
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−0.4 −0.3 −0.2 −0.1 0 0.1 0.2 0.3 0.4 0.5 0.60
10
20
30
40
50
60
Vector−MUSICQ−MUSIC
first source
second source
−0.4 −0.3 −0.2 −0.1 0 0.1 0.2 0.3 0.4 0.5 0.60
5
10
15
20
25
30
35
40
45
50
Vector−MUSICQ−MUSIC
second source
first source
DOA by θ rad DOA by θ rad
(a) (b)
Fig. 5. DOA estimation using Q-MUSIC and Vector-MUSIC
(a) Cut forρ1 = 2.5, ϕ1 = −0.18 rad (source #1)
(b) Cut for ρ2 = 3, ϕ2 = 0.15 rad (source #2)
−0.4
−0.2
0
0.2
0.4
1.5
2
2.5
3
3.5
40
10
20
30
40
50
60
Phi (rad)Rho
V−
MU
SIC
am
plitu
de
(− 0.18) (2.5)
−0.4
−0.2
0
0.2
0.4
1.5
2
2.5
3
3.5
40
10
20
30
40
50
60
Phi (rad)
Rho
Q−
MU
SIC
am
plitu
de
(− 0.18) (2.5)
First source polarization plan (θ1 = 0.48 rad) First source polarization plan (θ1 = 0.48 rad)
by Vector-MUSIC by Q-MUSIC
(a) (b)
Fig. 6. Polarization estimation for the first source using Q-MUSIC and Vector-MUSIC
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−15 −10 −5 0 5 10 15−50
−48
−46
−44
−42
−40
−38
−36
SNR (dB)
RM
S e
stim
atio
n er
ror
Scalar−MUSICQuaternion−MUSICVector−MUSIC
Fig. 7. RMS estimation error (dB) for
θ versus SNR (dB)
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