Physics 101: Lecture 21, Pg 1 Physics 101: Lecture 21 Waves.
Lecture 21
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Transcript of Lecture 21
Lecture 21
OUTLINE
The MOSFET (cont’d) • P-channel MOSFET• CMOS inverter analysis• Sub-threshold current• Small signal model
Reading: Pierret 17.3; Hu 6.7, 7.2
P-Channel MOSFET• The PMOSFET turns on when VGS < VT
– Holes flow from SOURCE to DRAIN DRAIN is biased at a lower potential than the SOURCE
• In a CMOS technology, the PMOS & NMOS threshold voltages are usually symmetric about 0, i.e. VTp = -VTn
P+ P+
N
GATEVS VD
VG
ID
VB
• VDS < 0
• IDS < 0
• |IDS| increases with
• |VGS - VT|
• |VDS| (linear region)
EE130/230M Spring 2013 Lecture 21, Slide 2
DSDSTpGSeffpoxeDS VVm
VVCL
WI )
2(,
Long-Channel PMOSFET I-V
• Linear region:
• Saturation region:
2, )(
2 TpGSeffpoxeDsatDS VVCmL
WII
m
VVV
TpGS
DS
0
m
VVV
TpGS
DS
m = 1 + (3Toxe/WT) is the bulk-charge factor
EE130/230M Spring 2013 Lecture 21, Slide 3
CMOS Inverter: Intuitive Perspective
VDD
Rn
VIN = VDD
CIRCUIT SWITCH MODELS
VDD
Rp
VIN = 0V
VOUT = 0V VOUT = VDD
Low static power consumption, sinceone MOSFET is always off in steady state
VDD
VIN VOUT
S
D
G
GS
D
EE130/230M Spring 2013 Lecture 21, Slide 4
Voltage Transfer Characteristic
VIN
VOUT
VDD
VDD00
N: offP: lin
N: linP: off
N: linP: sat
N: satP: lin
N: satP: sat
A B D E
C
EE130/230M Spring 2013 Lecture 21, Slide 5
CMOS Inverter Load-Line Analysis
VOUT=VDSn
IDn=-IDp
0
IDn=-IDp
–V
GSp =VIN -V
DD
+
VIN = VDD + VGSp
increasingVIN
increasingVIN
VIN = 0 V VIN = VDD
VDD
VOUT = VDD + VDSp
VDSp = 0VDSp = - VDD
–
VDSp=VOUT-VDD
+
0
EE130/230M Spring 2013 Lecture 21, Slide 6
VOUT=VDSn
IDn=-IDp
00
Load-Line Analysis: Region A
VIN VTn
IDn=-IDp
–V
GSp =VIN -V
DD
+
–
VDSp=VOUT-VDD
+
VDD
EE130/230M Spring 2013 Lecture 21, Slide 7
00
Load-Line Analysis: Region B
VDD/2 > VIN > VTn
IDn=-IDp
–V
GSp =VIN -V
DD
+
–
VDSp=VOUT-VDD
+
VOUT=VDSn
IDn=-IDp
VDD
EE130/230M Spring 2013 Lecture 21, Slide 8
00
Load-Line Analysis: Region D
VDD – |VTp| > VIN > VDD/2IDn=-IDp
–V
GSp =VIN -V
DD
+
–
VDSp=VOUT-VDD
+
VOUT=VDSn
IDn=-IDp
VDD
EE130/230M Spring 2013 Lecture 21, Slide 9
00
Load-Line Analysis: Region E
VIN > VDD – |VTp|IDn=-IDp
–V
GSp =VIN -V
DD
+
–
VDSp=VOUT-VDD
+
VOUT=VDSn
IDn=-IDp
VDD
EE130/230M Spring 2013 Lecture 21, Slide 10
MOSFET Effective Drive Current, IEFF
NMOS DRAIN VOLTAGE = VOUT
VIN = VDD
NM
OS
DRA
IN C
URR
ENT
VDD0.5VDD
IDsat
V2 IEFF =IH + IL
2tpHL
tpLH
V1 TIME
VDD
VDD/2V1 V2 V3
CMOS inverter chain:V3
VIN = ½VDD
IH
ILGND
VDDS
S
D
DVIN
VOUT
CMOS inverter:
M. H. Na et al., IEDM Technical Digest, pp. 121-124, 2002
EE130/230M Spring 2013 Lecture 21, Slide 11
Propagation Delay, d
d is reduced by increasing IEFF and reducing load capacitance C
CMOS inverter chain: VDD
VDD
Voltage waveforms:
EFF
DDpLHpHLd I
CVtt
22
1
EE130/230M Spring 2013 Lecture 21, Slide 12
Sub-Threshold Current• For |VG| < |VT|, MOSFET current flow is limited by carrier
diffusion into the channel region.
• The electric potential in the channel region varies linearly with VG, according to the capacitive voltage divider formula:
• As the potential barrier to diffusion increases linearly with decreasing VG, the diffusion current decreases exponentially:
mkTqVDS
GeI /
EE130/230M Spring 2013
GGdepoxe
oxeC V
mV
CC
CV
1
Lecture 21, Slide 13
Sub-Threshold Swing, S
)1)(10(
)(log
min,
1
10
oxe
dep
GS
DS
C
Cln
q
kT
dV
IdS
EE130/230M Spring 2013 Lecture 21, Slide 14
Inverse slope is subthreshold swing, S[mV/dec]
log ID
VT
VGS0NMOSFET Energy Band Profile
incr
easi
ng E
distance
n(E) exp(-E/kT)
SourceDrain
increasing VGS
VT Design Trade-off
EE130/230M Spring 2013 Lecture 21, Slide 15
• Low VT is desirable for high ON current:IDsat (VDD - VT) 1 < < 2
• But high VT is needed for low OFF current:
VT cannot be aggressively reduced!
Low VT
High VT
IOFF,high VT
IOFF,low VT
VGS
log ID
0
MOSFET Small Signal Model• Conductance parameters:
)(
0
TGSoxeeff
constVG
Dm
Dsat
constVD
Dd
VVmL
CW
V
Ig
IV
Ig
D
G
gmddd vgvgi
EE130/230M Spring 2013
A small change in VG or VDS will result in a small change in ID
Lecture 21, Slide 17
low-frequency:
high-frequency:
MOSFET Cutoff Frequency, fT
Higher MOSFET operating frequency is achieved by decreasing the channel length L
)(22 2 TGS
eff
oxe
mT VV
mLC
gf
EE130/230M Spring 2013 Lecture 21, Slide 19
The cut-off frequency fT is defined as the frequency when the current gain is reduced to 1.
input current = GGvCj
output current = Gmvg
vG here is ac signalCG is approximately equal to the gate capacitance, W L Cox
At the cutoff frequency (T = 2fT): 12
GGT
Gm
vCf
vg