INTERACTIVE GRAPHICS IN LOW-NOISE CIRCUIT DESIGN · 2015. 5. 22. · 5.3.3 Equivalent input noise...
Transcript of INTERACTIVE GRAPHICS IN LOW-NOISE CIRCUIT DESIGN · 2015. 5. 22. · 5.3.3 Equivalent input noise...
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INTERACTIVE GRAPHICS IN LOW-NOISE CIRCUIT DESIGN
BY
MOHAMMAD YOUSUF
OCTOBER, 1978
A THESIS SUBMITTED FOR THE DEGREE OF
MASTER OF PHILOSOPHY OF THE UNIVERSITY
OF LONDON
DEPARTMENT OF ELECTRICAL ENGINEERING
IMPERIAL COLLEGE OF SCIENCE AND TECHNOLOGY
LONDON S.W.7
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ABSTRACT
The thesis discusses a computer-aided low-noise electronic design facility which uses interactive graphics.
The dc-analysis has been made to form an integral part of the noise analysis, due to the additional importance of the quiescent point on circuit noise behaviour. After the dc-analysis, results are displayed as transistor currents and circuit node voltages on the CRT .screen (superimposed on the circuit diagram).
Hybrid-Tr models are formed for each transistor at the quiescent point. Of course, the circuit designer can simulate other models of transistor or of any other devices at any arbitrary quiescent point.
Two shot noise sources (at the quiescent point) and one thermal noise source are simulated for each transistor. Also, one thermal noise source (at room temp.) for each resistor in the circuit is simulated automatically.
The automatic noise source simulation can be overridden either by making a resistor noiseless or re-defining the noise temperature.
Also, simulation of shot noise sources at any arbitrary quiescent current value is possible.
Among the analysis facilities, are the small-signal gain-phase response and a plot of output noise voltage against frequency. All the noise sources in the circuit can be replaced by a single equivalent input noise source at the signal source point and its value plotted over any band of frequency. Both the noise voltage at the output and the equivalent input noise voltage can be integrated to give the total noise within a band. To enable the circuit designer to identify and to deal with the major noise contributing components, individual noise contributi-ons from each component can be displayed by value or by symbol (superimposed on the component). One analysis program plots noise figure against source resistance with the latter around its optimum value.
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ACKNOWLEDGEMENT
I am deeply grateful to Dr. R. A. King for his
encouragement, help and useful criticisms throughout this
work. N
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LIST OF SYMBOLS
SYMBOL
DEFINITION
k Boltzmann's constant
T Temperature
B Bandwidth
In Mean square noise current
Vn Mean square noise voltage
q Charge of an electron
If Mean square flicker noise current
C Correlation coefficient
G The gain from the input port to the output port
Gt The gain from input signal source to output port
VT (kT)/q
cv 2Trf
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CONTENTS
PAGE
ABSTRACT
1
ACKNOWLEDGEMENT
2
LIST OF SYMBOLS
3
CHAPTER 1 INTRODUCTION
7
CHAPTER 2 NOISE MECHANISMS AND NOISE SOURCE
MODELLING 13
2.1 NOISE MECHANISMS 13
2.1.1 Thermal noise 13
2.1.2 Shot noise 15
2.1.3 Low-frequency noise 15
2.2 CORRELATION 16
2.3 SIMULATION OF NOISE SOURCES 17
2.3.1 Resistor 18
2.3.2 Semiconductor diode 18
2.3.3- Bipolar transistor 19
2.3.4 Field-effect transistor 20
2.4 SUMMARY 23
CHAPTER 3 INPUT OF CIRCUIT DATA, AND OUTPUT OF
ANALYSIS RESULTS BY USING INTERACTIVE
GRAPHICS 24
3.1 THE GRAPHIC-15 DISPLAY SYSTEM
24
3.2 THE GRAPHIC-15 INSTRUCTIONS
27
3.3 CIRCUIT DATA INPUT
29
3.3.1 The display file 2y
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PAGE
3.3.2 Starting the circuit diagram drawing 31
3.3.3 The tracking cross operation 33
3.3.4 The grid-structure and circuit
diagram data management 36
3.3.5 Component selection from the 'menu' 40
3.3.6 Scaling the circuit diagram 42
3.3.7 Moving the circuit diagram on the
screen 42
3.3.8 Assignment of values to the circuit
elements 43
3.3.9 Deletion and erasing 43
3.4 NOISE DATA INPUT 44
3.4.1 Assignment of shot noise parameters 44
3.4.2 Assignment of thermal noise parameters 45
3.4.3 Deleting and clearing the assignments-- ssignments - 47
3.4.4 Simulation of noise sources for the
bipolar transistor 48
3.4.5 The noise parameter assignment program 48
3.4.6 The display file for displaying
assignments 55
3.5 ANALYSIS RESULTS OUTPUT 59
3.6 SUMMARY 60
CHAPTER 4 NONLINEAR DC-ANALYSIS
62
4.1. NEWTON-RAPHSON ITERATION TECHNIQUE 63
4.2 MODIFICATIONS TO THE NEWTON-RAPHSON ITERATION
TECHNIQUE 65
4.3 TRANSISTOR MODELLING FOR THE DC-ANALYSIS 67
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4.4 IMPLEMENTATION OF THE DC-ANALYSIS PROGRAM 69
4.5 SUMMARY 76
CHAPTER 5 NOISE AND GAIN-PHASE ANALYSES 77
5.1 SMALL-SIGNAL MODELLING OF THE BIPOLAR
TRANSISTOR 77
5.2 USE OF INTERRECIPROCITY CONCEPT FOR NOISE
ANALYSIS 79
5.3 ANALYSIS OPTIONS 85
5.3.1 .Noise at output 86
5.3.2 Noise contribution 88
5.3.3 Equivalent input noise 90'
5.3.4 Optimum source resistance 93
5.3.5 Integration of noise at the output
and of equivalent input noise 96
5.3.6 Small-signal gain and phase analysis 97
5.4 SUMMARY 99
CHAPTER 6 CONCLUSIONS 100
APPENDIX A THE OVERLAY STRUCTURE FOR THE
SUBROUTINES 103
APPENDIX B SEQUENCE OF PROGRAM SELECTION BY
THE USER 106
REFERENCES • 109
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CHAPTER ONE
INTRODUCTION
Computer-aided circuit design is an iterative
process in which the circuit designer and the computer need
to work in close partnership to achive good results. Either
side has capablities that complement the other. After the
design objectives and the specifications have been set,
the circuit designer using his experience and imaginative
power synthesizes a trial circuit. Then he inputs the
circuit data to the computer and asks for an analysis. The
computer with its ability to work reliably and at a high'
speed and with its enormous capacity to hold information
in the memory is well suited for the job. The computer
analyses the trial circuit and outputs the analysis results
to the circuit designer, who compares the predicted circuit
performance with the set objectives and specifications.
It is highly likely that the objectives and the
specifications will not be met fully. Again, the circuit
designer will use his experience and creativeness to
modify the trial circuit and ask the computer for another
analysis. Thus the iterative loop (shown in Fig. 1.1 - by a
flow-chart) is repeated. To facilitate good design this
loop traversing should be smooth and speedy.
In a situation where the circuit designer is one
of the users in the 'queue' for a computer operating in a
batch mode he may have to wait for hours to get the circuit
analysis results or sometimes only to be told that the
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designer circuit
Set objectives
and specifications
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Circuit Synthesize a trial
Input circuit data
to the computer
Analyse
the circuit
Computer
Output results
to the designer
Circuit
performance
acceptable Circuit
designer Yes
Modify the
trial circuit
Design acceptable
Fig. 1.1 Flow-chart for the computer-aided circuit
design iterative loop.
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analysis could not be carried out due to error in input
data. Apparently, undesireable delay is introduced in the
iterative design process loop.
By using an on-line computing facility (either
a small computer used by the circuit designer alone or a
large computer system used with other users on a
time-sharing basis) the delay can be considerably reduced
and a good interaction with the computer is achievēd.
Human beings perceive information easily when
presented in the pictorial form rather than in the
alphanumeric form. Engineers have been using 'drawing'
for design purposes for many years. But with a computer
system without any interactive graphics(a facility using
which one can exchange information with the computer via
the console of a CRT type display), it is necessary to
translate a circuit diagram into a (often quite rigidly)
formatted alphanumeric form to be fed into the computer.
It is a both unusual and troublesome job on the part of a
circuit designer. The possiblity of a mistake being commit-=
ted during this translation process is also present.
On the other hand, a computer system which has
interactive graphics facility and will allow the circuit
designer to 'draw' a circuit diagram on the face of a CRT
with a light-pen in very much the same way as he would do
on a piece of paper with a pencil, will save a lot of
trouble and time. The facility will also greatly reduce the
possiblity of feeding in erroneous input data. As an
example, if a mistake is made by putting a capacitor in
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CE CE
Fig. 1.2 Capacitor placed in place of the emitter
resistor.
place of the emitter resistor (Fig. 1.2), it is highly un-
likely that this will escape the circuit designer's
notice when he makes a check on the circuit diagram. But
it is quite possible to overlook a 'C' typed by mistake
in place of 'R' in a mass of alphanumeric data.
Noise is a problem in communication, measurement
and control systems. Very often a signal carrying
essential information is weak. The weak signal needs to be
amplified before it can be used properly. Also some form of
transducer or sensing device is required to convert a
non-electrical signal into an electrical one (e.g. a
microphone to convert acoustic signal into electrical
signal) for the amplifier. The sensor that picks up the
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signal alsd picks up noise. With an ideal noise-free
sensor and amplifier, the signal to noise ratio at the
output of the amplifier is the same as that at the input
of the sensor. But in the real world, both the sensor and
the amplifier will have noise mechanisms associated with
them. As a result, the signal to noise ratio at the output
will be degraded. A Je.signe7 of low-noise circuits tries to
keep this signal to noise ratio degradation to a minimum
and to achieve that he can use the power of a digital
computer.
Any ac-analysis program such as ECAP[1] can be
used for the noise analysis of a circuit. In such a case,
the noise sources are considered one at a time and the
circuit analysed by using superposition to obtain the
total output noise for all noise sources. Obviously, this
is a very expensive way. An experienced low-noise circuit
designer with his intuition can reduce the number of
analyses by considering only the important noise sources.
A much better way is to use the transpose circuit method [26]
which requires a- little more computation than that required
for one circuit analysis and still considers all the noise
sources in a circuit.
But for a low-noise design of electronic
circuits, noise calculation and presentation need to be
done in various forms (for example, the total output noise
within a frequency band, the equivalent input noise, etc.).
A computer program 'NOISE'[2] for low-noise
design is reported to have been found useful by the design
engineers. But 'NOISE' has some limitations. It can take
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into account only the noise sources of the input stage.
for circuit noise calculation, resulting in loss of
accuracy. Also, the circuit data and the noise data have
to be inputted in a rigidly formatted alphanumeric form.
For example, an input data card must have values at all
specified locations, even if some of them may not be used
for noise analysis; and, to quote "Harmless constants must
be provided for those locations on the card". Also, the
output of the results are in a not-easily-comprehensible
form (i.e. in numbers).
The purpose of this research work was to design
a flexible and easy-to-use 'low-noise circuit design
facility' by exploiting the benefits offered by the
interactive graphics. Also, the noise sources of all the
stages are considered (the transpose circuit method is
used for noise analysis). The dc-analysis is made to form
an integral part of this noise analysis facility, because
of the dc-operating point's influence on both circuit
response and the noise mechanisms.
'Chapter two' is a brief discussion of different
kinds of noise mechanisms. 'Chapter three' describes how
the input of circuit data and noise data are made to the
computer; and also how the computer outputs the analysis
results. 'Chapter four' is on nonlinear dc-analysis,which
is carried out to find the dc-operating point. 'Chapter
five' describes how the small-signal hybrid-TC transistor
model is formed, at the dc-operating point. Also, the
different noise analyses and the gain-phase analysis
facilities are discussed. 'Chapter six' -is the conclusion.
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CHAPTER TWO
NOISE MECHANISMMS AND NOISE SOURCE MODELLING
For the design of low-noise electronic circuits,
it is necessary to understand the characteristics of noise
sources and minimize their effects.
2.1 NOISE MECHANISMS
The main three noise mechanisms, namely—
the thermal noise, the shot noise and the low-frequency
noise are discussed. For more details references [3]to_[8]
may be consulted.
2.1.1 Thermal noise
Thermal noise is generated by the random motion
of charge carriers in an element whose impedance has a
resistive part. J. B. Johnson observed this noise first
in 1927 and the theoretical analysis was p:'oduced by H.
Nyquist in 1928. Thermal noise is also known as Nyquist
noise or Johnson noise. Nyquist found out that the
available noise power from a resistor is proportional to
the product of the temperature (in.K) o:Z the resistor and
the bandwidth over which the noise measurement is carried
out.
Available noise power= kTB
where, k= Boltzmann's constant
T= Temperature (°K)
B= Bandwidth (Hz)
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The thermal noise spectral density (defined as
the mean square noise voltage per hertz of bandwidth) when
plotted against frequency, gives a flat curve A resistor
of resistance R ohm which has an open-circuit mean square
noise voltageVn can be modelled as a noiseless resistor
of value R ohm in series with a voltage source of value
V~ as shown in Fig. 2.1.1a.
(a) (b)
Fig. 2.1.1 Thermal noise source modelling;
(a) by voltage source and (b) by current source
The available noise power from the voltage source is the
power dissipated by a resistor of value R ohm connected
between the terminals 'A' and 'B', and is given by V„/4R
But as mentioned before, the available thermal noise
power from a resistor is equal to kTB.
Therefore, V, /(4R) = kTB
and hence,
'k 7he
`vn = 4kTRB
šz_Í flzeFuenay fev5anse 1s Õ'a* oL'elz cL Lin;tad /a.?cle-O alfl .
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The thermal noise from the resistor R can, alternatively,
be represented by a noise current source (Fig. 2.1.1b)
having a mean square value given by the following expression
= 4kTB/R
2.1.2 Shot noise
The noise associated with the motion of charge
carriers across a potential barrier is called shot noise.
This noise is present in thermionic valves, semiconductor
diodes and transistors. As an example, in a vaccum tube
diode this noise is due to the fact that charge carriers
are discrete and their random arrival at the anode of the
valve causes small pulses of current.
The mean square shot noise current in a semi-
conductor diode is equal to 24IB
where, q = charge of an electron
I = quiescent current of the diode
B = bandwidth of noise measurement
Like thermal noise, shot noise power per hertz of
bandwidth is constant at all frequencies LT to uery, ki9h rectuenc;es .
2.1.3 Low-frequency noise
This is the type of noise which is dominant
below about 1 kHz. The spectral density is nearly
proportional to 1/f and therefore, this type of noise is
sometimes referred to as 1/f noise. This noise was first
observed in vaccum tubes and was referred to as 'flicker
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effect' . Hence this noise is also called flicker noise.
The main cause of the low-frequency noise is
the generation and recombination of charge carriers on the
surface of and at discontinuities in the semiconductor
device material. Improved surface treatment of the,semi-
conductor material has reduced this type of noise. Unlike
thermal noise and shot noise, the flicker noise cannot be
predicted by a simple analytic expression.
Flicker noise in transistors has been investiga-
ted[9] . In a bipolar transistor this noise mechanism can
be represented by a current source connected across the
internal base-emitter junction having a mean square value
given by the following expression
If = KIB B
The value of IX is about 1. Although K and?' vary from unit
to unit, they can be measured[101 for several units,
typical values formed and used for a particular process.
2.2 CORRELATION
Noise sources resulting from independent physical
mechanisms are independent of each other or uncorrelated.
But inter-dependent physical mechanisms .or even the same
physical mechanism can give rise to noise sources which
may be correlated. If we consider two noise sources with
instantaneous voltage values of V1 and v. connected in
series as shown in Fig. 2.2, then the root mean square
voltage of the resultant equivalent noise source can be
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Vr
V1
V2
Fig. 2.2 Two noise sources connected in series.
expressed as
Vr=Vi+VZ +2CI✓ \/
where, C = V,Vz
I/ 2
v' v22
I
C is called the correlation coefficient and its value lies
between -1 and +1. If two signal sources have voltage
waveforms of identical shape, then the sources are said to
be 100% correlated and the value of C becomes 1. For two
uncorrelated noise sources the correlation coefficient C is
equal to 0.
2.3 SIMULATION OF NOISE SOURCES
The noise mechanisms are simulated by noise
current sources because nodal analysis method has been used
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for circuit solution. 1» -0,i's work attention is res4ricked fo low fre.luen fi re/ior where hL9k frequency s{fea-ts liave bee„ ignoted..
2.3.1 Resistor
The thermal noise of a resistor is simulated by
a noise current source In in parallel with the resistor
as shown in Fig. 2.3.1 .
Rhoisy)
Fig. 2.3.1 Simulation of noise source for a resistor.
2.3.2 Semiconductor diode
At the quiescent operating point, a semiconductor
diode can be represented by an ohmic resistance P1 in series
with a dynamic resistance P2 as shown in Fig. 2.3.2 .
The thermal noise due to the ohmic resistance and the shot
noise due to the quiescent diode current are simulated by two
noise current; sources Ini and Int respectively.
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Idc
Fig. 2.3.2 Simulation of noise sources for a
semiconductor diode.
2.3.3 Bipolar transistor
A noise model for a bipolar transistor at
frequencies upto about 100MHz will include one thermal
noise source, one 1/f noise source and two shot noise
sources. The thermal noise source is due to the base
spreading resistancerbb, and is simulated by the noise
current source Inbb' (Fig. 2.3.3). One of the two shot
noise sources is due to the quiescent base current'B
and the other shot noise source is due to the
quiescent collector current Ic and they are simulated by
two noise current sourcesjnbez between the nodes }3',E and
Ince between the nodes.C,E respectively. The flicker noise
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b' Intiei
A
is simulated by the noise current sourcelnbe1, between
the nodes B',E .
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B rbb' B'
ce Dince
Vbbe
l E
Inbb' = 4 k TB/r6g
Intiez = 2gIB B
=KIB f B
Ince = 2q Ic B
Fig. 2.3.3 Simulation of noise sources for a bipolar
transistor.
2.3.4 Field-effect transistor
The field-effect transistor operates on the
principle of channel conductance modulation. And associated
with this channel conductance is the thermal noise mechani-
sm which can be simulated by a noise current source
connected between the drain and the source (Fig. 2.3.4) .
nb'ez
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The mean square value of this current source is given by
Inc = 4 k T9mo ad B
9mo is the maximum value of gm (the FET transconductance)
and is given by
gmo ` Vp
where, IDSS is the value of drain current at saturation
for zero gate voltage and
Vp is the pinch-off voltage (the gate voltage
which is capable of reducing the channel
width to zero for small drain-source voltage).
For MOSFET ad is equal to 2/3 (approx.) and for JPET ad - is
a function of biasing condition and a typical value is 0.65.
2 IDSS
Drain Gate 0
Vg s
Source
Fig. 2.3.4 Simulation of noise sources for a field-effect
transistor.
In add tion to the above the thermal noise in the
IF Cgd
nc ant ds irds Cgs g vg5 ngi
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channel induces noise in the gate due to the capacitive
coupling between the gate and the channel. This induced
gate noise has been analysed for the JFET (11] and the
MOSFET [12]. The mean square values of the noise currents
for the two types of devices (JFET and MOSFET) are given
by similar expressions
f 2
In9i = 4 k T L C99
ai B gmo
where, Cgc = gate to channel capacitance caused by
depletion layer in JFET and by oxide
layer in MOSFET.
ai = 0.12 (approx.) for MOSFET and is
dependendent on bias conditions with a
typical value of 0.3 for JFET.
This noise mechanism can be simulated by connecting a noise
current source between the gate and source (Fig. 2.3.4).
This induced gate noise becomes significant at high
frequencies (at about 1MHz).
The 1/f noise mechanism in a JFET is due to the
generation and recombination of charge carriers in the
depletion layer. While, the main cause of 1/f noise mechani-
sm in a MOSFET is related with the surface states at the
interface between the semiconductor and the oxide. This
noise mechanism can be simulated by connecting a noise
current source between the drain and the source. The low--
frequency noise in MOSFET devices are much higher compared
to that of the JFET and therefore, MOSFET devices are
unsuitable for low frequency operation.
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The 1/f noise in a JFET can be simulated by a noise current
source connected between the drain and the source [13] ,
having a mean square value given_ by the following expression
en ID If =K
where, K is a constant for a given JFET (at a given
temperature),
Q is a constant for a particular JFET and
ID is quiescent drain current.
2.4 SUMMARY
The three main types of noise namely; thermal
noise (caused by the random motion of electrons), shot
noise (associated with the motion of charge carriers
across a potential barrier) and the low-frequency noise
(caused mainly by the generation and recombination of
charge carriers on the surface of the semiconductor device
material) are discussed. Then the equivalent noise source
resulting from the uncorrelated sources and the correlated
sources is discussed. And finally, the simulation of the
noise mechanisms by the noise current sources is discussed.
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CHAPTER THREE
INPUT OF CIRCUIT AND NOISE DATA,
AND OUTPUT OF ANALYSIS RESULTS BY USING INTERACTIVE GRAPHICS
The input of circuit data and noise data to the
computer is made by using the light-pen and the CRT screen
as .much as possible and the use of the teletype is kept at
a minimum. This is done to take advantage of the ease and
speed offered by the interactive graphics in communicating
with the computer. Monitoring of the progress of analysis,
error message displays and analysis results displays are
made on the CRT screen...
In our noise analysis facility some graphics
subroutines, (for example, the subroutine for circuit data
input (sec. 3.3), the subroutine for producing the
octagonal symbols for noise contribution display
(Fig. 5.3.2a), etc.) with modifications where necessary
from a circuit analysis package MINNIE [14], have been
used. Some graphics programs, for example, the program
needed to monitor the progress of the nonlinear dc-analysis
(Fig. 4.4b), noise parameter assignment display (sub. sec.
3.4.5), etc. have been.designed to meet our requirements.
3.1 THE GRAPHIC-15 DISPLAY SYSTEM
The Graphic-15 display system [15] comprises the
VT15 graphic processor, VT04 graphic display console and a
light-pen. The VT15 graphic processor is a subordinate to
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the PDP-15 computer. The photograph below (Fig. 3.1a)
shows an user using the Graphic-15 display system. The
light-pen is an input device and the display console is
an output device of the graphic processor. Fig.3.lb is a
block diagrammatic representation of the PDP-15 computer
and the Graphic-15 display system. Also, there are six
pushbuttons on the display console which give additional
control over the graphic system operation. The display
system of the Graphic-15 is a directed-stroke (unlike the
raster-type TV display) refreshed display system. The
directed-stroke system allows easy and quick generation
of CRT display of any real-time light-pen motion on the
CRT screen. The light-pen is connected via a flexible light
guide to a photomultiplier. This combination produces an
output only from the light
Fig. 3.1a Photograph showing an user using the Graphic-15 display system.
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caused by the writing electron beam and not from the
after-glow light when the electron beam has moved past
the point. The light-pen has a mechanical shutter on it
which is used to prevent any unwanted light from entering
the light guide. The CRT screen on the display console
is 11* in the horizontal direction and 9h in the -
DATA AND CONTROL BUS
PDP-15 I/O BUS
C >
PDP-15
VT15
VT04
COMPUTER
GRAPHIC PROCESSOR
ANALOG BUS
DISPLAY' CONSOLE
Fig. 3.1b Block diagrammatic representation of the PDP-15 computer and the Graphic-15 display system.
vertical direction (Fig. 3.1c). The screen is divided into
two areas— the major image area (or the main area) and the
minor image area (or the offset area). By appropriate use
of the Graphic-15 instructions the movement of the CRT
electron beam is controlled and the necessary graphic
display is constructed.
As the Graphic-15 display is refresh type, for
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MAJOR IMAGE AREA OR MAIN AREA
Y-axis
Origin
0///////j X-axis >
9 /2
MINOR IMAGE AREA
OR
OFFSET AREA
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any graphic construction to be displayed on the screen,
there must be some local memory to hold the display file
(the display file is a program for the graphic processor),
so that the graphic processor can cycle through the display
file continuously. In this case, the local memory is the
main memory of the PDP-15 computer which is 32K of 18-bit
words of core memory.
Htc 11/24--->i
Fig. 3.1c CRT screen on the display console.
3.2 THE GRAPHIC-15 INSTRUCTIONS
These are the instructions that the VT15 graphic
processor executes. As an example, one of these instructions
is the basic vector instruction. This instruction is 18-bit
long and its bit format is shown in Fig, 3.2a . The three
bits in bit-positions 0-2 form the operation code and tell
the graphic processor what to do (in this case to draw a
basic vector). The vector can be made light-pen sensitive
or insensitive by setting the bit in bi(;-position 3,to 1 or
k 912
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1 0 0
Vector direction
Vector length
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0 respectively. If the bit in bit-position 4 is set to 1
then the vector is drawn visibly and if the bit is set to
0 the vector is drawn invisibly. By setting the three bits
in bit-positions 5-7 appropriately the vector can be drawn
2
1. 0
6
Fig. 3.2b Basic vector directions
0 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17
Light-pen Intensity
Fig. 3.2a Basic vector instruction bit format.
in any one of the possible eight directions (Fig. 3.2b).
The 10 bits in bit-positions 8-17 are for the specification.
of the vector length. The vectors are drawn from the last
position of the electron beam on the CRT screen.
The 'point; plot' ins t ruction in its 10 bits in
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bit-positions 8-17 specify the electron beam displacement
on the CRT screen, from the origin, either along the x-axis
or along the y-axis specified by the bit in bit-position 6.
This instruction is used to position the electron beam at
some desired point on the CRT screen. The VT15 graphic a
processor has Ahardware character generator. By using - the
'character string' instruction any 'text' can be displayed
on the screen.
Then there are 'parameter' instructions. Using
these instructions, the intensity of the vector(s) or
character(s) can be set to any one of the possible eight
levels. Any one of the 16. scale factors can be chosen (this
feature is used for scaling the graphic construction), The
vector(s) or character(s) can be blinked or rotated.
3.3 CIRCUIT DATA INPUT
3.3.1 The display file
The display file is the program for the graphic
processor and is- formed out of the graphic processor
instructions. The digital instructions are converted into
analog signals that drive the x- and y-axis deflection
circuits of the CRT display. As an example, the display
file needed to produce the capacitor symbol. of Fig. 3.3.1a
must contain seven vector instructions. The dotted lines
represent the unintesi.fied vectors. Like this capacitor
symbol, other component symbols are needed to be able
to 'draw' the circui .diagram on the CRT screen. A 'menu'
is formed with the component symbols and is displayed
in the offset area of the screen (Fig. 3.3.1b).
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2A
1
3
6
7
5
Fig. 3.3.1a Capacitor symbol.
Component symbols will also appear in the circuit diagram
and usually more than once. Therefore, instead of repeating
the display files for the component symbols, they are made
in the form of subroutines.
Menu
Group 1
Group 2 Group 3
No. 4 No. 5
No. 6
No. 7
Fig. 3.3.1b Circuit diagram drawing with the light-pen.
-
} } 4- 4- r 4- }t 4,4
-7w
+ 4- t -y -s• 4- .4- t i J
31
These subroutines are called from a master display file
whenever a component symbol needs to be displayed One such
master file is the display file for the circuit diagram. -
3.3.2 Starting the circuit dia ram drawing
At the beginning of the circuit diagram drawing,
the user must select a point on the screen of the CRT at
which the drawing is to start. When a light-pen is pointed
(a) (b)
Fig. 3.3.2 'Nēt' pattern generated to find (a) the x-co- ordinate and (b) the y-coordinate of the light-pen hit point.
at the CRT screen with its shutter open, it 'see's a:-
circular area (the field of view of the light-pen). As the
light-pen is a passive device, the presence of a writing
electron beam on the screen and within its field of view is
necessary for it to serve any useful purpose. At the
beginning the CRT screen is blank. Therefore, a graphic
pattern is generated which is made up of a series of
-
32
vectors and looks like a 'net' (Fig. 3.3.2a). Now, if the
light-pen is pointed at the 'net' pattern (with its shutter
open), as soon as the writing electron beam comes within
the field of view of the light-pen, the light-pen flag is
raised by the graphic processor. Immediately, the PDP-15
causes the graphic processor to halt.
The graphic processor has two position registers
-- the x-position register and the y-position register.
When the graphic processor is halted these two registers
hold the x- and y-coordinate values of the end of the vector
that was being drawn. The PDP-15 reads the x-position
register to get the x-coordinate of the light-pen hit
point. Then the PDP-15 modifies the 'net' display file
and restarts the graphic processor. This time, a slightly
different 'net' pattern is produced (Fig. 3.3.2b), Now,
as soon as the writing electron beam comes within the
field of view of the light-pen, the graphic processor and
the PDP-15 take the same set of actions, with the only
•exception that the register is read by the
PDP-15 to get the y-coordinate of the light-pen hit point.
Now both the x-coordinate and the y-coordinate of the light-
pen hit point are known. The 'net' pattern is removed.
A 'tracking cross' is displayed at the point of
the light-pen hit. Also, the component 'menu' is displayed
in the offset area of the screen. If the light-pen is
pointed at the tracking cross (with the shutter open)
and moved on the CRT screen, the tracking cross follows
the light-pen.
-
Light-pen's field of view
Centre of light-pen's field of view
Tracking cross
X c -71 X X2 )/2
Yc =(Y, +Y2)/2
33
3.3.3 The tracking cross operation
The field of view of the light-pen is a circular
area (Fig. 3.3.3a). When the light-pen is moved away from
the tracking cross, the computer needs to know the new
position of the centre of the field of view of the light-pen
in order to be able to move the tracking cross there.
Fig. 3.3.3a The tracking cross and the field of view of the light-pen.
Following is a description of how the x- and the y-
coordinates Xc andYc respectively of the centre of the light-
pen's field of view aie determined.
-
Arm no.1 < < ( <
x
/
/ /
/
A
Start
< < < < < < <
34
The tracking cross has four intensified arms
(Fig. 3.3,3b). Arm no.2 and arm no.4 are drawn side by
side in the figure for the sake of clarity, but in the
actual case the electron beam draws them along the same line
on the CRT screen. That is also the case with arm no.1
and arm no.3
p4Finish i
/4
V
Arm no.2 Arm no.4 /
Arm no.3 • • \
• • • \
• •
/
`\ / \ / \ / ♦ / ♦R V .. )/
\ I • / \ \ Y A /
♦ / • / ♦
Fig, 3.3.3b The construction of the tracking cross.
The light-pen is switched on (using graphic
processor instruction) before drawing each of the four arms.
Now, if the light-pen is pointed at the tracking
-
35
cross (Fig. 3.3.3a and Fig. 3.3,3b), as soon as the
electron beam while drawing arm no.1 enters the field of
view of the light-pen, the graphic processor raises the
light-pen flag and the PDP-15 receives an interrupt signal.
Immediately, the light-pen is switched off and the graphic
processor is halted. The x-position register is read to get
the value of X2 (Fig.3.3.3a). Then the graphic processor
will resume operation and draw the rest of arm no.1, with
the light-pen still switched off, to prevent any more
light-pen interrupt taking place on this arm. At the
completion of the drawing of arm no.1, the light-pen is
switched on and 'arm no.2 is drawn. During the process of
arm no.2 drawing, the same set of events take place, with
the only exception that this time the y-position register
is read to get the value of Y2. (Fig. 3.3.3a). Then arm no.3
and finally arm no.4 are drawn to get the values of Xi and
Y . Now the coordinates Xc and Yc are calculated and the
tracking cross is moved to this new position.
The whole process is repeated over and over again
as the light-pen is moved over the CRT screen and the
tracking cross keeps on following the light-pen.
Although, the tracking cross can be moved to any
point on the screen by tracking cross operation, while
circuit drawing the movements of the tracking cross and the
circuit diagram are allowed only along the lines of a
grid-structure. This is done to facilitate the management
of the circuit diagram data.
-
36
3.3.4 Thegrid-structure and circuit diagram date.
management
The grid-structure is made up of 25 vertical
lines (each having a particular Ml value in the range from
1 to 25) and 25 horizontal lines (each having a particular
N'value in the range from 1 to 25). Four vertical and four
horizontal lines are shown by dotted lines in Fig. 3.3.4a.
I I I I I I I
1 1 1 1 1 1 I 1
N=g ----------1-- 1 -----+---- '
1 1 1 I 1 I I I I 1 1 I
N =g -- i -----t I I 1 1
ii
-
37
For a horizontal path K'is equal to 1 and for a vertical
path Ke is equal to 2. The M/ and Nfi index numbers for both
of the paths are the same as that of their intersection
point (i.e. M= 4 and N= 7) . A path can be a node or a branch.
In figure 3.3,4b three paths are shown, two of them are
branches and the third one is a node.
The information about a path is kept in an 18-
bit word and this is explained with reference to figure
3.3.4c.
4 5 6 7 8 9 10 11 12 13 14 15 16 17
J
Branch or node number.
A value to calculate the address corresponding to this path in the display file.
Branch or node.
Fig. 3.3.4c One 18-bit word containing information about a path.
The bit in bit-position 0 is set to 1 if the path is a
branch and 'is set to 0 if the path is a node. The seven bits
in bit-positions 1-7 contain the branch or node number. The
ten bits in bit-positions 8-17 contain a number which is
used to calculate the addresses of a group of words in the
master display file,for the circuit diagram. A path array
is formed with such 18-bit words (figure 3.3.4d).
-
10 bit
38
First word First word
Group of words corresponding
714th word
to a path
18 bit 18 bit >
Displa-cement value
This 10 bit contains the displac-ement value
Fig. 3.3.4e The master display file for the circuit diagram.
Fig. 3.3.4d The path array.
-
39
Corresponding to any path there are three path indices--
Mt, N and K. Using these three path indices, the address
of the word in the path array corresponding to the path
in question is calculated in the following way:
Address of the Address of the word in the = 50M + 2N
/+ K
/- 53 + first word in
path array the path array
As an example, let it be supposed that a capacitor symbol
is displayed at the position of the path having indices
M p =15, N~ =8 and K~ =1 as shown in Fig. 3.3.4d. The address
of the word in the path array corresponding to this path
is given by,
Address of the Required address = 50*15 + 2*8 + 1 -53 + first word in
the path array
= 714+ [Address of the first word in the path array
The 10 bits in the word at this address hold a 'displacement
value' (Fig. 3.34e) used to calculate the address of the
group of words corresponding to this path, in the master
display file for the circuit diagram. One word of this
group is a 'call' to subroutine. In this particular case,
the subroutine is the display file for the capacitor symbol.
The other words in L.he group contain such information as
whether to blink the component symbol or not, whether the
component symbol is to be drawn vertically or horizontally,
etc.
-
40 •
3.3.5 Component selection from the Menu'
During the circuit diagram drawing process,
components have to be selected from the component menu
displayed in the offset area of the screen (figure 3.3.1b).
There is a 7-bit hardware register called the 'name
register' in the graphic processor. Using graphic processor
instructions any number from 0 to 127 can be loaded into
this register. The content of this register can be read by
the PDP-15 and, depending on the value, appropriate
branching action can be taken in the program. The name
register is loaded with different values before drawing
each of the component symbols.
As an example, the name register can be loaded
with the number 1 by an instruction which is followed by an
instruction making a 'call' to the display file subroutine
for the capacitor symbol. Then another instruction causing
the number 2 to be loaded into the name register and follo-
wed by an instruction 'call ing the subroutine for the
resistor symbol display file. Let it be assumed, that these
four instructions form a part of a master display file
(for displaying offset area 'picture'). Now if the light-
pen is pointed at the capacitor symbol, then as soon as
the writing electron beam comes within the field of view of
the light-pen, the graphic processor is halted and the
content of the name register is read to find out which
component symbol was hit. This is illustrated by the
flow-chart of figure 3.3.5.
-
Halt the graphic processor
Yes
it component is a capacitor
Yes
Load the 'name register' with 1
41
Draw the capacitor symbol and wait for a light-pen hit
Light-pen hit
No light-pen hit
Load the 'name register' with 2
Draw the resistor symbol and wait for a light-pen hit
Light-pen hit
No light-pen hit'
Fig, 3.3.5 Flow-chart illustrating the identification of component symbols hit by the light-pen.
-
42
3.3.6 Scaling the circuit diagram
One of the instructions of the graphic processor
allows any vector to be repeated upto 15 times. Using this
facility a graphic construction can be enlarged upto 16
times its original size.
Normally the circuit diagram is drawn with a
scale factor of 2 (i.e. the vectors are three times their
original size). Using a light-button called ZOOM (button
no.5 in Fig. 3.3.1b), the scale factor can be increased or
decreased and thereby the circuit diagram enlarged or
reduced. If the left-hand side of the ZOOM button is hit
with the light-pen the scale factor is reduced by 1 and if
the right-hand side of this button is hit the scale factor
is increased by 1.
3.3.7 Moving the circuit diagram on the screen
When the scale factor is equal to 3 or greater,
the size of the grid-structure is larger than the CRT screen
area. With this !situation the screen acts as a 'window'. To
look at or to draw a circuit on the part of the grid-
structure which is not within the 'window', the grid-
structure has to be moved. Using the 'move circuit' light-
button (button no.7 in Fig. 3,3,1b), the grid-structure
and hence the circuit diagram can be moved on the CRT screen.
At first, the 'move circuit' light-button is selected with
the light-pen. Then, the light-pen is pointed at the circuit
diagram and the tracking cross appears under the light-pen.
Now, if the light-pen is moved on the screen of the CRT,
-
43
the tracking cross and the circuit diagram moves with the
light-pen.
3.3.3 Assignment of values to the circuit elements
Values to.the circuit elements can be assigned
either by using the light-pen and the light-buttons or the
light-pen and the teletype. The light-pen is used to select
the circuit elements and the light-buttons. The light-
buttons are in the offset area of the CRT screen and have
some preferred values on it (Group 1 in Fig. 3.3olb). Also
there are some light-buttons each having a multiplication
factor associated with it (Group 2 and Group 3 in
Fig. 3.3.1b). For example, selection of the light-button
4.7 from Group 1 and *100 from Group 2 will result in a
value of 470 and this can be assigned to a circuit element
by hitting the element with the light-pen.
3.3.9 Deletion and erasing
Any part of the circuit diagram can be deleted
using the light-button DELETE (No.4 in Fig. 3,3.1b).
Any component or line hit by the light-pen, with this light-
button selected will be deleted. There is another method of
. deletion which can be used while drawing the circuit diagram.
If the light-pen is moved back over any existing line or
component (excepting the three-terminal ones) from the open
end, the line or component is deleted,
The 'erase circuit' light--button (No.6 in
Fig. 3.3.1b) can be used Lu deleLe Lhe euLire circuit;
-
44
diagram at the same time. If a light-pen hit is made on
this light-button a warning message appears on the CRT
screen and the computer ask for confirmation. Now a second
hit on this button will result in the entire circuit diagram
being erased. While, any other action by the user will cause
the first hit (on the 'erase circuit' light-button) to be
ignored.
3.4 NOISE DATA INPUT
Thermal and shot noise sources are simulated for
the purpose of noise analysis. For each circuit component
which is responsible for causing either thermal or shot
noise mechanism, a noise current source is formed and
connected across the component. This noise current source
is not displayed with the circuit diagram. Noise parameters
are assigned to the circuit components and are used to
calculate the noise current source values.
3.4.1 Assignment of shot noise parameters
For the simulation of shot noise sources (sub.-
sec. 2.1.2) the value of the quiescent current is necessary.
In the offset area of the screen, there are light-buttons
for making the assignments of noise parameters. Under the
heading '*SIIOT NOISE' is the light-button 'NOISE CURRENT'
(No.3 in Fig. 3.4a). If this light-button is selected with
the light-pen, a 'box' (No.4 in Fig. 3.4a) appears under
the light-button indicating that a value is needed for the
quiescent current (to calculate the shot noise current).
Then this current value can be assigned to the intended
-
~---No.2
( No.5
( No.6
Fig. 3 0 4a Assignment of noise parameters to circuit components 0
45
component by hitting the component with the light-pen. The
assigned quiescent current value is displayed beside the
component as an indication to the user that the component
has received the value and also for future reference.
3.4.2 Assignrnent of thermal noise parameters
For the simulation of the thermal noise source
(sub.-sec. 2.1.1), the resistance and the temperature of the
resistor are needed. The resistance values are already
assigned to the resistors during circuit data input. There
are two light-buttons (No.1 and No.2 in Fig. 3.4a) under the
heading '*THERMAL NOISE'. The second of these two light-
-
46
buttons is the 'TEMPERATURE' light-button. Using this light-
button any temperature value in °C can be assigned to a
resistor. When this button is selected a 'box' appears
below it, indicating that a value for the temperature is
needed. When this value is typed-in (via the teletype) it
is stored (in the computer memory) and displayed within the
'box'. The value is assigned to a resistor and displayed
beside it, when a light-pen hit on the resistor is made.
Components having ohmic resistance and at a
temperature higher than °0 K will have thermal noise. And
usually there will be many such components (resistors) in a
circuit. Therefore, at the beginning (of noise data input
stage) thermal noise is assigned to all resistors automati-
cally. In this automatic thermal noise source simulation
room temperature value is used. Using the 'TEMPERATURE'
light-button this room.temperature value can be changed to
any temperature value. The first of the light-buttons under
the heading '*THERMAL NOISE' is the 'NOISELESS-RESISTOR'
button. Selection of this button and a subsequent light-pen
hit on any resistor will result in a label 'NLR'
(Noiseless resistor) being put beside the resistor and the
resistor will have no thermal noise contribution. This
facility is necessary in cases where dynamic resistances
are present in a circuit, because they will be represented
by resistors in a circuit diagram, and autom:.tic assignment
of thermal noise will be made to them.
When any one of the three light-buttons----
'NOISELESS-RESISTOR', 'TEMPERATURE' or 'NOISE CURRENT' is
selected the relevant labels on the circuit components
-
4?
are displayed at a higher intensity level for ease of
identification. As an example, in Fig. 3.4a in the photogr-
aph the 'NOISE CURRENT' light-button is selected and as a
result the noise current values displayed beside the compo-
nents in the circuit diagram are at a higher intensity
level.
3.4.3 Deleting and clearing the assignments
There is a light-button called 'DELETE' (No.5 in
Fig. 3.4a). Using this button any parameter assignments can
be cancelled. When the 'DELETE' button is selected a flash-
ing 'box' is displayed around this button as a warning to
the user. For example, to cancel any temperature assignment,
this button is selected alongwith the 'TEMPERATURE' button.
Then a light-pen hit on a resistor having temperature
assignment will result in temperature being restored -to
room temperature. In this way any number of assignments can
be cancelled. But cancelling many or all the assignments
in this way will be a tedious job. Therefore, another option
has been created: There is a light-button called 'CLEAR'
(No.6 in Fig. 3.4a) and using this button all assignments
can be cancelled simultaneously. There is a lock to
prevent any accidental cancellation. A first light-pen hit
on this light-button causes a warning message ("CLEAR ALL
ASSIGNMENTS ? PLEASE CONFIRM.) to be displayed. At this
stage, a light-pen hit on any other light-button will
cause the first hit on the 'CLEAR' button to be ignored,
the warning message to be removed and appropriate action
depending on the light-button hit to be taken. On the other
-
48
hand, if a second hit is made on the 'CLEAR' button then
all the assignments will be cancelled.
3.4.4 Simulation of noise sources for the bi.olar
transistor
Three noise sources --- one thermal and two shot
noise sources are simulated for a bipolar transistor (sub.-
sec. 2.3.3). The base spreading resistance and the quiescent
operating condition need to be known. The base spreading
resistance value is obtained from the transistor data
library (sec. 5.1).
With a circuit which has bipolar transistor as
a circuit component, as soon as the 'circuit definition'
(circuit drawing) stage is cancelled,the nonlinear
dc-analysis (chapter 4) is automatically selected. At the
end of the dc-analysis, the quiescent collector and base
currents are stored for later use. The stored quiescent
current values are used for shot noise source simulation.
For the simulation of these three noise
sources the user does not need to do anything.
3.4.5 The noise parameter assi•nment rogram
The flow-chart for the noise parameter assignment
program is broken down into four parts and shown in
Fig. 3.4b, Fig. 3.4c, Fig. 3.4d and Fig. 3.4e. This program
is selected by pointing the light-pen at the 'ASSIGN NOISE'
light-button (Fig. 5.3 ). As the execution of this program
starts (see flow-chart of Fig. 3,4b), the light-buttons and
-
49
the circuit diagram are displayed as in Fig. 3,4a.
Thermal noise is assigned to all the resistors
(at room temperature) and then a waiting point is reached.
The computer waits here until a light-pen hit occurs.
If a light-pen hit occurs a test is made to determine
whether the hit was in the main area or the offset area of
the CRT screen.
If the hit is in the offset area of the screen,
the control goes to the part of the program whose flow-chart
appears in Fig. 3.4c. The hit light-button is sorted out
first. If the 'NOISE ANALYSIS' light-button is hit the
control returns from this program (i.e. the noise parameter
assignment program) and goes to 'circuit definition'
program which is for circuit data input. If the 'ASSIGN
NOISE' light-button is hit the control returns from this
program and goes to the program from where either this
program or other analysis programs as shown in Fig. 5.3
can be selected (see Appendix B). For a light-pen hit on
any other light-button, appropriate action is taken and the
control goes to in Fig. 3.4b where it waits for a further
light-pen hit.
Of the three light-buttons, namely, 'NOISELECS-
RESISTOR', 'TEMPERATURE', and 'NOISE CURRENT' (Fig. 3.4a)
only one can be selected at any time. For example, if the
'TEMPERATURE' light-button is selected and then a light-pen
hit is made on the 'NOISELESS-RESISTOR' light-button; the
former will be cancelled and the later will be selected.
Of course, most of the light-buttons can be cancelled by
-
50
hitting it a second time with the light-pen.
Now, if a light-pen hit occurs on the circuit diagram, a test is made to see if the 'DELETE' light-button
is already selected. This 'DELETE' button can be selected
in conjunction with any one of the three light-buttons
already mentioned (NOISELESS-RESISTOR', 'TEMPERATURE' and
'NOISE CURRENT'). If this light-button is not selected the,
the control goes to the section of the program whose
flow-chart is shown in Fig. 3.4d. This section of the
program is used to make noise parameter assignments, and
some error checks are also made here. For example, the
temperature assignment to any component other than a
resistor is not permitted. At the completion of a parameter
assignment to a component the control goes back to in in
Fig. 3.4b.
If the 'DELETE' light-button is selected and a
light-pen hit is made on the circuit diagram, the control
goes to the part of the program whose flow-chart appears
in Fig. 3,4e. This section of the program is for the
cancellation of any noise parameter assignment. When the
user cancells an assignment, the program restores the state
of the circuit element that existed before that particular
assignment was made. For example, if the user cancells the
'no thermal noise' assignment to a resistor, the program
will assign to the resistor thermal noise at room
temperature.
-
0 comes from of Figs. 3.4c, 3.4d and 3.4e.
Assign thermal noise at room temperature to all resistors.
Yes
51
{
Display the light-buttons and the circuit diagram (as in Fig. 3.4a)
On the circuit On the light-button
No
Yes
O2 goes to O2 of Fig. 3.4c.
3 goes to O3 of Fig. 3.4d.
O goes to O of Fig. 3.4e.
Fig. 3.4b Part of flow-chart illustrating noise data input.
-
52
Yes 'NOISE ANALYSIS'
button hit 9
Go to 'CIRCUIT DEFINITION' stage.
No
'ASSIGN NOISE' button hit
9
Yes
Go to the stage from where either 'ASSIGN NOISE' or any other noise analysis program can be selected.
No
Yes •'NOISELESS-RESISTOR'
button hit 9
Select this button and cancel any other button if selected.
Yes Select this button and cancel any other button if selected.
'TEMPERATURE' button hit
9
Yes Select this button and cancel any other button if selected.
'NOISE CURRENT' button hit
9
'DELETE' button hit
9
Yes Select this button, draw a blinking 'box' around it cancel 'CLEAR' button if selected and remove the warning message if on.
'CLEAR' button hit
9
Yes, 1st hit Display the warning message "CLEAR ALL ASSIGNMENTS ? PLEASE CONFIRM" .
Yes, 2nd hit
Clear all assignments, remove the warning message and cancel all the light-buttons..
of Fig. 3.4b
jr of Fig. 3.4b
O goes to (2 comes from
Fig. 3.4c Part of the flow-chart, illustrating noise data input.
-
Assign noise temperature. Make
'Noiseless-resistor' assignment.
~1 goes to
(3 comes from
in Fig. 3.4b
in Fig. 3.4b
53
'Noiseless-resistor' button selected
9
Yes
Is 'Temperature'
button selected 7
Is hit component a resistor
Yes
No
'Ignore.
Ignore.
No
Yes
Is 'Noise current' button selected
9
Ignore.
v Yes
Assign noise current.
Is hit component 'a resistor
Fig. 3.4d Part of the flow-chart illustrating noise data input.
-
54
Cancel 'shot noise' assign-ment only.
1O goes to
comes from
of Fig. 3.4b
of Fig. 3.4b
Is 'NOISE CURRENT' button selected
Yes Is it
a resistor with 'shot noise' and 'no thermal noise'
assignment
Ignore No
Restore to a resistor with 'thermal noise at room temp.' assignment.
Is it a resistor with
'no thermal noise' assignment
Yes
N
Ignore
Is 'TEMPERATURE' button selected
Yes
s it a resistor
with 'temperature' assignment
Yes
Ignore
N
Is it a circuit element with 'shot noise'
assignment only ?
Yes • ICancel 'shot noise' assignment.
Is 'NOISELESS-RESISTOR'
button selected
Yes
Fig. 3.4e Part of flow-chart iliustraLing noise data input.
-
55
3.4.6 The display .file for displaying assignments
A display file is formed to display the three
types of assignments— 'NLR' (for noiseless-resistor),
'temperature' and 'noise current'. From now on they will
also be referred to as type 1 (for 'NLR'), type 2 (for
'temperature') and type 3 (for 'noise current'). A group
of five consecutive words of memory is used to display
the assignment of one type to one branch. The groups
belonging to the same type are linked up. The relative
positions of the groups in the linked-up structure are
dependent upon the order in which the branches (to which
they correspond) were selected, when the assignments of
a particular type were being made. Whereas, the relative
positions of the groups in the memory locations are
dependent upon the branch numbers to which they correspond.
To explain the construction of a group, the
group 2 of type 1 (Fig. 3.4.6a) is discussed. All the groups
excepting the first and the last (to be discussed later)
are similar to this group. The second and the third words
contain instructions to position the electron beam near the
relevant branch position on the CRT screen. The instruction
in the fourth word writes the label 'NLR'. The fifth worn
has the instru ion to cause a jump to the second word of
the group 3 and this is how the link among the groups of a
type are maintained. The first-word of this group holds the
address of the first word of the group 1 (of type 1). And
this address is used, if the 'DELETE' light-button is used
to cancel the `NLR' assignment to branch no.3. Because then.,
-
Address of pointer group which points at 2nd word of this group
Move the beam along the x-axis
Move the beam along the y-axis
Display the 'NLR' label
Jump to 2nd word of group 2 of type 1
J
1 -4
-1
J 1
Address of 1st word of previous group of type 1
Move the beam along the x-axis
Move the beam along the y-axis
Display the 'NLR' label
Jump to 2nd word of group 3 of type 1
—1
1
56
Branch no 1 : Group 1 : Type 1
Branch no 2 : Group 1 : Type 2
Branch no 3 : Group 2 : Type 1
Branch no 4
Branch no 5 : Group 3 : Type 1
Branch no 6 : Group 2 : Type 2
Fig. 3.4.6a The linked-up groups of the type 1 and the type 2.
-
5?
group 2 is excluded from the linked-up groups of type 1 and
a new link is formed from group 1 to group 3.
The linked-up structure of the groups of type 2
is similar to that of the type 1.
Because a resistor cannot have the 'NLR' and the
'temperature' assignments at the same time, the same area
of the core memory can be shared by the linked-up structures
of the type 1 and • the type 2. A group can be removed from
the linked-up structure of type 1 and added to the linked-
up structure of type 2 and vice versa. This is done if the
'NLR' assignment of a resistor is changed to a 'temperature'
assignment and vice versa.
The linked-up structure for type 3 is similar
to that of the other two types . But as a circuit component
can have the 'NLR' and the 'noise current' assignments at
the same time, this linked-up structure is kept in another
part of the core memory.
Fig. 3,4.6b illustrates the way in which the
three linked-up structures of type 1, type 2 and type 3 are
interlinked. In the figure the groups of any one type have
been drawn as if they are adjacent and sequential, for
ease of illustration but in the real case they are unlikely
to be so.
There are three pointer groups---one for each of
the three types. The pointer group consists of two words;
the first word contains the intensity level instruction.
When a particular type is selected, the first word content
-
i
1st group
2nd group
Last group
Pointer group
Intensity level
Jump to 2nd word of group 1
Address of pointer group of type 1
Jump to pointer group of type 2
Pointer group
Intensity level
Jump to 2nd word of group 2
Address of pointer group of type 2
Jump to pointer group of type 3
1st group
2nd group
Last group
Pointer group
Intensity level
Jump to 2nd word of group 3
Address of pointer group of type 3
Go to another display file
Type 1 Type 2• Type 3
Fig. 3.4.6b The interlinking of the linked-up groups.
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59
of the pointer group corresponding to that type is modified.
For example, if the light-button 'TEMPERATURE' is selected
with the light-pen, then the instruction contained in the
pointer group of type 2 is modified to increase the
intensity level. As a result, any assignment displays)
caused by the group(s) of type 2 will become brighter. The
first word of the first group of any particular type holds
the address of the respective pointer group.
The last word of the last group of type 1 and
type 2 contain jump instructions to the pointer group of
the type 2 and type 3 respectively. Whereas the last word
of the last group of type 3 contain a jump instruction to
the start of the another display file (for example, the
circuit diagram display file or the light-button display
file).
3.5 ANALYSIS RESULTS OUTPUT
All circuit analysis results are outputted on
the CRT screen, in the form of numbers, graphs and symbols.
Analysis results that are calculated as a
function of a single variable (for example, output noise
voltage as a function of frequency) are well represented
by graphs (Fig. 5.3.1b).
The nonlinear dc-analysis results-- the quies-
cent node voltages and the nonlinear device currents are
shown by numbers. It is very useful for the user to be able
to 'see' the voltages and currents beside the nodes and the
devices concerned (Fig. 4.4d ).
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60
In some cases, it is not necessary to know the exact values
of some quantities, rather a knowledge of their relative
importance is more useful. In such cases, the various
quantities can be represented by symbols, the sizes of the
symbols being dependent upon the quantities they represent.
One such case is that of the relative importance of the
noise contributions of the various circuit components
(Fig. 5.3.2a).
3.6 SUMMARY
For the noise analysis of a circuit, information
about the circuit and the noise mechanisms are needed by
the computer. A Graphic-15 display system (consisting of a
graphic processor, a display console and a light-pen) and
a PDP-15 computer are used.
Circuit data is inputted by 'drawing' the circuit
diagram on the CRT screen of the graphic display console by
using the light-pen. The graphic processor executes its
program (called 'display file') and produces analog signals
for the x- and y-deflection circuits of the display console
which in turn controls the electron beam of the CRT.
When the light-pen, which is a passive device,
is pointed at the CRT screen a signal is sent to the compu-
ter if the writing electron beam passes through its field
of view. The position of the electron beam on the CRT screen
when the signal (to the PDP-15) was sent gives the point
at which the light-pen was pointed at. A graphic pattern
is generated in a systematic way on the blank screen, so
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61
that the user can select a starting point with the light-pen
for circuit diagram drawing. At the selected starting point
a 'tracking cross' is displayed, which serves two purposes
-----the first is to let the user know the latest position on
the screen the light-pen was moved to and the second is to
calculate the new position of the light-pen on the screen,
when the light-pen is moved. During the 'drawing' process,
circuit components are selected from the 'menu' displayed
on the screen. Value to the circuit components are given
either by using the light-buttons (with values on them) or
the teletype. Then there are such facilities as circuit
diagram deletion, enlargement, reduction etc.
The noise data are inputted by making noise
parameter assignments. Some assignments are automatically
made (by the computer). While other assignments are left
for the user to make. Any assignment can be changed to a
different type. Assignments can be cancelled one at a time
or all at the same time.
At the completion of the circuit analysis, the
results are displayed on the CRT screen by graph plots,
numbers and symbols.
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62
CHAPTER FOUR
NONLINEAR DC-ANALYSIS
If any nonlinear device like a semiconductor
diode or a transistor is present in an electronic circuit,
then it is necessary to know the quiescent operating point
by carrying out the nonlinear dc-analysis before any noise
or small-signal gain-phase analysis can be done. Also, the
values of the shot noise sources are directly dependent on
the quiescent currents of the diodes and the transistors.
The nonlinear dc-analysis requires the solution
of a set of simultaneous nonlinear equations. But due to
the highly nonlinear nature of the diode and the transistor
p-n junction characteristic, the solution of the equations
cannot be found by direct algebraic manipulation [16] .
The solution can be obtained by using the method of succe-
ssive approximations. Almost all of the presently available
nonlinear dc-analysis programs use algorithms based on the
Newton-Raphson iteration technique.
Two efficient analysis programs BIAS-3 [17J and
CANCER [15] capable of nonlinear dc-analysis have been
reported. The program BIAS-3 is reported, to have been
tested quite extensively with different types of circuits
for more than a year and found reliable. Also, algorithms
similar to that of BIAS-3 have been used in several other
circuit analysis programs [19] , [20] , [21] and found fast
and reliable. For our nonlinear dc-analysis an algorithm
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63
similar to that of BIAS-3 has been used.
4.1 NEWTON-RAPHSON ITERATION TECHNIQUE
The standard Newton-Raphson iteration technique
can be explained with a simple diode-resistor circuit.
(Fig. 4.1a). At first, a trial operating point is selected
Fig. 4.1a The diode-resistor circuit.
at some point (vd0'Ido)
on the nonlinear diode characteristic
(Fig. 4.1b). The nonlinear characteristic is then replaced by
a straight line which is tangent (to the nonlinear character-
istic) at the operating point. This is equivalent to approxi-
mating the diode by an independent current source in parallel
with a linear conductance. The value of the conductance is gi-
ven by the slope of the tangent and the value of the current
source is given by the intercept on the diode current axis.
The solution of the circuit with the approximated
diode gives the new diode voltage Vd1 (at the point P1) . When
this point is projected vertically up, the second trial ope-
rating point (v, , idi ),is obtained. Now, the nonlinear cha-
-
V/R
t
Id
64
racteristi.c is linearized at the second trial operating poi-
nt and the circuit is solved which leads to the third trial
operating point (Vd2, Id2). A linearized characteristic and
circuit solution at the third trial operating point leads to
the fourth and finally the real operating point P4 is found.
Vd V
Fig. 4.1b Illustrating the standard Newton-Raphson iteration.
The standard Newton-Raphson iteration is not
suitable for the solution of problems where rapidly varying
functions such as exponentials have to be evaluated. • As
with the diode-resistor case, a small increase in the
junction voltage causes a much greater increase in the
-
V/R
Id
V Vd
Fig. 4.1c Modified NewLon-Raphson iteration technique.
65
diode current and may even result in computer word-overflow
as illustrated in Fig. 4.1c.
4.2 MODIFICATIONS TO THE NEWTON-RAPHSON ITERATION
TECHNIQUE
One way of getting round the possible numerical
ill-conditioning (word-overflow) is to use a method [17] ,
which will now be described. At first, a trial operating
point is guessed at Pb (Fig. 4.1c).
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66
After linearizing the circuit at the first trial
operating point P0 , the circuit is solved and the point P1
is obtained. Now instead of projecting the point P1
vertically up, it is projected horizontally on the nonlinear
characteristic and the second trial operating point ( v d1 Idl ) is obtained. Mathematically, this is done by taking
the logarithm of the currentIdlcorresponding to the point
Pl , which yields voltage vd1.
This method of updating with current, not only
avoids the possiblity of computer word-overflow, but also
reaches the actual operating point in less number of
iterations by damping the magnitude of the increasing
junction voltages. When the junction voltage decreases and
also when the junction voltage is negative, updating of the
operating point is done with voltage as in the standard
Newton-Raphson iteration.
The magnitude of the decreasing junction voltage
can be reduced by introducing a damping factor.
Another problem is the numerical ill-conditioning
(computer word-underflow) due to very small value of the
slope of the linearized characteristic when the value of
the junction voltage is very sm211 or negative. This-
problem has been taken care of in BIAS-3 by drawing a
straight line between the trial operating point and the
origin instead of the tangent.
Whereas in the computer program CANCER, for
junction voltages less than 10VT (where, VT =kT/q) instead
of making the value of the linear conductance equal to the
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67
slope of the tangent, it is given the value of 10.0E-12
Siemens but the value of the independent current source is
calculated in the usual way.
4.3 TRANSISTOR MODELLING FOR THE DC-ANALYSIS
The well-known Ebers-Moll bipolar transistor
model [22] , [23] is shown in Fig. 4.3a.
o Collector
VBC
Base
VBE IF
Emitter -I E
Fig. 4.3a Ebers-Moll bipolar transistor model.
The currents through the diodes are
I = I exp VBE !- 1 F ES VT j- and IR _ ICS eXp VT
which are also the reference currents for this model. IES
and ICS are the emitter-base and collector-base saturation
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68
currents respectively. aF and aR are the large-signal
forward and reverse current gains of a common-base
transistor. The diodes represent the two junctions of the
transistor and the two current-controlled current sources
represent the couplings between the two junctions.
The transistor model of Fig. 4.3a can be slightly
modified and the mathematically equivalent model of
Fig. 4.3b is obtained.
• Collector
VBC O ICC
I Base •
VBE ICC /aF IEC
Emitter
IE
Fig. 4.3b Slightly modified Ebers-Moll bipolar transistor model.
For the model of Fig. 4.3b the reference currents are the
currents of the controlled sources;
ICC __ (*F
IES 7.3
vBEI - 1 and ~ ! T j
-
I
Base
VBC
69.,
VBC
IEC __ aR ICS exp V
1 T
The transistor model of Fig. 4.3b can be simpli-
fied and the following nonlinear hybrid-Tr model of Fig. 4.3c
is obtained.
Collector
IEC /RR
Q ICC (DIEC
VBE 0
• Emitter IE
/RF
SF = aF/(1-(F) and = aR/(1-aR)
Fig. 4.3c Nonlinear hybrid-Tr transistor model.
This nonlinear hybrid-Tr transistor model has been used in
the dc-analysis program.
4.4 IMPLEMENTATION OF THE EC-ANALYSIS PROGRAM
At the beginning, the light-buttons (as in
Fig. 4.4a) are displayed on the CRT screen_ At this stage
-
Fig. 4. 4a Photograph illustrating the application of supply voltage to a circuit.
it is necessary to assign supply voltage to the circuit.
70
If the light-button 'SUPPLY VOLTAGE' is hit with the light-
pen a 'box' appears just below this light-button. Any value
typed-in on the teletype appears within this 'box'. Then
if any node (of the circuit) is hit with the light-pen,
the supply voltage is assigned to that particu~ar node and
is displayed beside the hit point on the node.
A light-button called 'DELETE' (Fig. 4.4a) has
been provided to enable the user to remove a supply voltage
which might have been applied by mistake.
Now, the circuit is ready for analysis and a
light-pen hit on the button 'START ANALYSIS' (above Figure)
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71
starts the process.
At the start of the iteration, transistor
junction voltages are initialized. The base-emitter junction
is forward biased with 0.4 volt and the base-collector
junction is given 0.0 volt. Then if any inductor is present
in the circuit, the nodes between which it is connected are
short-circuited and the nodes are re-numbered (after the
dc-analysis the circuit is returned to its original configu-
ration }. Then the transistors are linearized at the trial
operating point and the nodal admittance matrix of the
circuit is formed. The node voltages of the nodes to which
grounded supply voltages are connected, are known and the
nodal admittance matrix is reduced in the following way.
If the supply voltage is connected to node 'm'
then the mth column of the nodal admittance matrix is
multiplied by the supply voltage value and subtracted from
the node current source vector. The mth row and the mth
column of the nodal admittance matrix are deleted. Then
Gaussian elimination method is used to evaluate the node
voltages.
At this stage the 'error voltage' defined as
Error voltage =(Vnew-Vold)IVold
is calculated for each node. The subscripts 'new' and 'old'
refer to the present and the previous iterations respective-
ly. At the end of an iteration, there are always two sets of
node voltages--- the 'new' set is the result of the present
iteration and the 'old' set is the result of the previous
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72
iteration; excepting the first iteration when the 'old' set
contains only zeros.
If each one of the 'error voltage's is less than
or equal to 1.0E-6 the iterative process is stopped.
Otherwise, the new trial operating point is selected and
the next iteration is carried out.
During the dc-analysis, the progress can be
monitored on the CRT screen. Both the error voltage and the
iteration number are displayed (in the offset area of the
screen) as shown in Fig. 4.4b..
Fig. 4.4b Monitoring the progress of the dc-analysis.
The photograph of Fig. 4.4b shows the error
voltage after the dc-analysis has completed the third
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73
iteration. In the photograph of Fig. 4.4c, it can be seen
that the error voltage has gone down after the completion
of the fifth iteration.
Fig. 4.4c Monitoring the progress of the dc-analysis.
As the error voltage can have a very wide range
of values wi th a minimum of 1 .. OE-6, the logari thm of the
error voltage is taken and displayed with a shifted scale
to make the minimum value zero.
(Error voltage)" = loglq(Error voltage) +6 .0
The scale is divided into eight divisions. Any value greater
than eight is taken as eight.
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74
At the end of the iterations, when the dc-
analysis results are obtained, the iteration number and
the error voltage displays are removed. In their place two
new light-buttons-- 'NODE VOLTAGE' and 'COLLECTOR CURRENT'
are displayed as shown in Fig. 4.4d. The process up to here
is flow-charted in Fig. 4.4e.
Fig. 4.4d Photograph showing dc-analysis results display.
To know the quiescent collector current (or the
node'voltage), the light-button 'COLLECTOR CURRENT' (or
'NODE VOLTAGE') is selected. After selecting the light-
button 'COLLECTOR CURRENT', if a transistor is hit with
the light-pen the collector current of the transistor is
displayed beside the transistor as shown in above Figure.
Similarly, the node voltages can be displayed.
-
f
1
Display circuit diagram and' dc-analysis light-buttons.
Has the supply-voltage been
applied
Yes
Is 'START ANALYSIS' button
hit 9
Yes
Initialize transistor junction voltages.
Short-circuit inductors (if any), and re-number nodes.
Linearize the transistors and form the nodal admittance matrix.
Solve the matrix to get the new set of node voltages.
Yes
Stop iteration.
Display error voltage and iteration number.
Select the new trial operating point.
Stop displaying error voltage and iteration number.
Display two new light-buttons.
75
Fig. 4.4e Flow-chart illustrating ān ūray ;z is... .
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76
4.5 SUMMARY
Nonlinear dc-analysis is essential for circuits
having nonlinear components (like diodes and transistors)
before noise analysis and small-signal gain-phase analysis.
Iterative methods based on Newton-Raphson iteration
technique are almost always used for the nonlinear do--
analysis. Modifications to the standard Newton-Raphson
iteration technique are necessary to avoid possible numeri-
cal ill-conditioning (computer word- overflow and underflow)
and also to speed up the iterative process. Nonlinear
hybrid-Tr model based on the well known Ebbers-Moll bipolar
transistor model has been used in our analysis program.
Supply voltages to the circuit are applied using the
teletype and the light-pen. During the dc-analysis the
'progress' is monitored on the CRT screen. The result of
the analysis can be seen as node voltages' and transistor
currents' values on the screen.
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77
CHAPTER FIVE
NOISE AND GAIN-PHASE ANALYSES
While designing a low-noise amplifier, the
circuit designer needs to know the noise analysis results
(such as, output noise, equivalent input noise, etc.) and
also the gain and the bandwidth of the synthesized
amplifier. So one of the available analyses is the small-
signal gain and phase analysis. But to carry out this
analysis (and also the noise analysis), the small-signal
linearized circuit description (the nodal admittance matrix)
is needed. Nonlinear dc-analysis is required for a circuit
which contains nonlinear component(s) to know the quiescent
operating point. Then the small-signal model(s) of the
nonlinear device(s) are formed at the dc-operating point
and used to form the linearized circuit description.
5.1
'SMALL-SIGNAL MODELLING OF THE BIPOLAR TRANSISTOR
A hybrid-Tr model is formed for each bipolar
transistor as shown in Fig. 5.1. For each transistor a new
node (B') is created. Following is a description of how the
hybrid-Tr model element values are determined.
The transconductance gm is given by the following
relationship
gm = (q/kT)lIcl
-
where, q = electronic charge,
k = Boltzmann's constant,
T = temperature in °K and
IC = quiescent collector current.
78
Cb
I I
rbbi
B C
.Cb'e eigmv
i E
Fig. 5.1 The hybrid-7r model for the bipolar transistor.
The element rb l e is determined using the relationship
rb'e = hfe /gm
The hybrid parameter h is a function of collector current. fe
The information about the variation of hfe with collector
current is stored in the form of an equation in a data-
library. The data-library was formed with the manufacturer's
supplied data for the transistor 2N3904. Also, in the data-
library are information about the variations of iire with
V r ce
rbc 'VNM,
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79
collector current, the gain-bandwidth product fT with
collector current and the output capacitance of the
transistor in the common-base configuration Cob with
reverse base-collector voltage. The value of rbc is obtained
from the following relationship
rbc rbe ihre
For the value of Cbl the value of Cob is used. For accurate
value of Cbē it is necessary to know the value of the
overlap-diode capacitance and the header capacitance from
high frequency y-parameter measurement [24]. To find the
value of Cbe the following relationship is used
Cbe [g
m '(27fT )] - Cb%
The base spreading resistance rbb can be measured
using different techniques. But as the main purpose of
transistor modelling here is to predict noise p