CLIC related CERN-KEK collaboration J.P.Delahaye for the CLIC study team.
26 Nov. 2010 Alexej Grudiev, CLIC DR RF system at 2 GHz. Conceptual design of the CLIC DR RF system...
-
Upload
isabella-glenn -
Category
Documents
-
view
220 -
download
2
Transcript of 26 Nov. 2010 Alexej Grudiev, CLIC DR RF system at 2 GHz. Conceptual design of the CLIC DR RF system...
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
Conceptual design of theCLIC DR RF system at 2 GHz
Alexej Grudiev
26.11.2010CLIC meeting
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
Acknowledgements
E. Jensen (CERN) W. Hofle (CERN) K. Akai (KEK)
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
Outline
Introduction High stored energy rf system
Normal conducting Superconducting
Low stored energy rf system Summary
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
Introduction
1 GHz option, current baseline since March 2010
DR
DLTo RTML
DR
To RTML
2 GHz option
Specs from RTML F. Stulle, CLIC meeting, 2010-06-04
To first order, in steady-state, the energy spread σE/E will be zero BUT the bunch-to-bunch separation can differ from 0.5 ns due to transient beam loading
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
CLIC DR RF parameters
E
Veh
Rp
Veh
V
U
h
EVe
h
EVeE
EE
srfp
rev
srfrevs
rf
s
p
rfrf
sss
2
cosˆ
2
cosˆ
ˆsin
ˆ2ˆ2
sin)2(cos
1
0
1
2
0
0
CLIC DR* NLC DR+
Circumference: C [m] 420.56 223
Bunch population: Ne 4x109 7x109
Energy : E [GeV] 2.86 ~2
Momentum compaction: αp 7.6x10-5 ?
Energy loss per turn: U0 [MeV] 4.2 0.635
RF frequency: frf [GHz] 1 2 0.714
RF voltage: Vrf [MV] 4.9 4.6 1
Calculated RF parameters
Harmonic number: h 1402 2804
Synchronous phase : φs [o] 59 66
Energy acceptance: ΔE/E [%] 2.29 1.08
Synchrotron frequency: fs
[kHz]2.76 3.36
• *from Yannis on 9/07/2010
• + from Tor et.al., PAC95
C L I CC L I C
9 March. 2010Alexej Grudiev, CLIC DR RF.
CW klystron power supply
LEP klystron power supply
3 phases main 12 phases – 600 Hz ripples
4%
filter
t t
f
600 Hz-40 dB
Filter reduce 600 Hz ripples down to
0.04*0.0045 = 2*10-
4
Feedback stabilizes high voltage at lower frequencies to the level of 1-0.1%. Limited mainly by the HV measurement accuracy
Information provided by D. Siemaszko
C L I CC L I C
9 March. 2010Alexej Grudiev, CLIC DR RF.
Klystron amplitude and phase stability
Beam voltage ~60 kVLow frequency high voltage stability: 0.1 % (0.3 % achieved in Tristan (KEK) DC power supply for 1MW CW klystron, PAC87)
-> 60V -> 1.2 kW rf output power stability~ 0.3 % power stability~ 0.15 % amplitude stabilityOr~ 1.2 degree phase stability
This is not sufficient (see RTML specs). Rf slow feedback loop around the klystron is necessary
High stored energy option
Beam cavity interaction, dV/V << 1V = Vrf + Vb = V*ejφ
dV = dVb*sinφs
Vdφ = dVb*cosφs
rf phase modulation versus rf amplitude modulation:
dφ = dV/(V*tanφs)
Vb
dVb
dVb
Vrf
V
φs
dφ
V
t
Energy los per turn: V0 = V sinφs
Beam cavity interaction, dV/V << 1
Trev tTb
Ib
2GHz case 1GHz case
Trev tTb
V 2GHz case
dV
Trev tTb
φb2GHz case
dφb
W = V2/2ρω; dW = dV 2V/ρωdW/dt = -Pb + ntrains*Tb/Trev*Pb ; dt -> Tb
dV/V = -PbTb(1-ntrainsTb/Trev)ρω/V2
dφ = dV/V*1/tanφs
dφs
V
φ
V0
V0 = V sinφs = energy loss per turn = const; dV0 = dV sinφs + Vcosφs dφs = 0dφs = - dV/V*tanφs
dφb = dφ+dφs = dV/V*(1/tanφs- tanφs)
dφ
KEKB RF systemK. Akai, et. al, “THE LOW-LEVEL RF SYSTEM FOR KEKB”, EPAC98
dV/V = PbTb(1-Tb/Trev)ρω/V2 ~ 1 % it is consistent with simulation presented in Fig 3
dφb = dV/V*(1/tanφs – tanφs) ~ 3o it is consistent with simulation presented in Fig 3
Dominated by direct cavity voltage phase modulation in KEKB case
π/2 - φs
THE ARES CAVITY FOR KEKB, Kageyama et al, APAC98Frequency: f[GHz] 0.509 1 2
Normalized shunt impedance (circuit): ρg=Rg/Q [Ω] (~f0)
7.5 7.5 7.5
Unloaded Q-factor: Q (~ 1/f1/2) 110000 77000 55000
Aperture radius: r [mm] (~ 1/f) 80 40 20
Max. Gap voltage: Vg [MV] (~ 1/f3/4)Nominal
0.5 0.3 0.18
Max. Gap voltage: Vg [MV] (~ 1/f3/4)High power tested times sqrt(3)
0.85 0.5 0.3
Wall loss per cavity: P=Vg2/2Rg
[MW]0.44 0.22 0.11
Scaling of the gap voltage is done to keep heat load per meter constant: P/g = Vg
2/2Rgg = Vg2/2ρgQ g => Vg ~1/f3/4
~2.5 m
CLIC DR parameters for scaled ARES cavity
Circumference: C [m] 420.56
Energy loss per turn: U0 [MeV] 4.2
RF frequency: frf [GHz] 1 2
RF voltage: Vrf [MV] 4.9 4.6
Beam current Ib [A] 0.66 1.3
Train length Tb [ns] 2 x 156 156
Harmonic number: h 1402 2804
Synchronous phase : φs [o] 59 66
Gap voltage: Vg [MV] 0.3 – 0.5 0.18 – 0.3
Wall loss total [MW] 1.2 - 2.1 1.0 - 1.7
Bunch phase spread for scaled ARES cavity: dφb [o] (ρg =7.5 Ω)
0.7 - 0.4 9 – 5.3
Specified bunch phase spread: dφb [o] 0.05 0.1
dV/V = -PbTb(1-ntrainsTb/Trev)ρgω/VgV
dφb = dV/V(1/tanφs-tanφs)
Specs from RTMLF. Stulle, CLIC meeting, 2010-06-04
Assuming parameters of ARES cavity from nominal up to tested (150 - 450 kW) and scaled to 1 or 2 GHz
Dominated by cavity voltage modulation
Solution 1: Modification of the scaled ARES cavity
Frequency: f[GHz] 0.509 1 2
Normalized shunt impedance (circuit): ρg=Rg/Q [Ω] (~1/f3)
7.5 0.95 0.12
Unloaded Q-factor: Q (~ f1/2) 110000 156000 220000
Aperture radius: r [mm] (~ 1/f) 80 40 20
Max. Gap voltage: Vg [MV] (~ 1/f5/4)Scaled to keep wall loss per cavity constant
0.85 0.35 0.15
Wall loss per cavity: [MW] 0.44 0.44 0.44
ρ=V2/2ω(Wa+Ws); in ARES Ws=10Wa
If we keep the size of the storage cavity the same as for 0.509 GHz when going to 1 or 2 GHz: Ws=10Wa*(f/0.509)3
ρ= 1/f3
In addition, Q-factor improves ~sqrt(f)
This implies that we go to higher order mode in storage cavity from TE015 to whispering-gallery modes like in the BOC-type pulse compressor.
Still, shunt impedance drops and wall losses per cavity increase significantly what requires gap voltage reduction.
Scaling of the gap voltage is done to keep heat load per cavity constant: P = Vg
2/2Rg = Vg2/2ρgQ => Vg ~1/f5/4
CLIC DR parameters for modified ARES cavity
Circumference: C [m] 420.56
Energy loss per turn: U0 [MeV] 4.2
RF frequency: frf [GHz] 1 2
RF voltage: Vrf [MV] 4.9 4.6
Beam current Ib [A] 0.66 1.3
Train length Tb [ns] 2 x 156 156
Harmonic number: h 1402 2804
Synchronous phase : φs [o] 59 66
Gap voltage: Vg [MV] 0.2 – 0.36 0.09 – 0.15
Wall loss total [MW] 3.5 - 6 7.9 - 13.4
Bunch phase spread for modified ARES cavities: dφb [o]
0.1- 0.07 0.28 - 0.17
Specified bunch phase spread: dφb [o] 0.05 0.1
Specs from RTMLF. Stulle, CLIC meeting, 2010-06-04
Assuming parameters of ARES cavity in the range from nominal up to tested and modified to 1 or 2 GHz keeping the same storage cavity volume
Performance is almost within specs but the power loss in the cavities is big. It is acceptable for 1 GHz but probably too big for 2 GHz
BUT the associated voltage reduction δV/V results in bucket reduction and consequently in bunch parameters modification. Radiation damping keeps σE=const for all bunches in the train so the bunch length varies along the train. The limit from RTML is that RMS{δσz /σz} < 1%
Solution 2: Mismatch of rf frequency and bunch frequency In the presence of linear phase shift of dφb over a period of time Tb : fb = frf - dφb/2πTb; To compensate dφb= dV/V (1/tanφs- tanφs) = 1.5o at 2 GHz, δV/V = -1%, φs=66o, dfrf/frf = -1.4e-5, very small
ΔE/Δz = σE/σz => ΔE σz = Δz σE Variation gives δΔE σz + ΔE δσz = δΔz σE+ Δz δσE
Which results in δσz /σz = δΔz/Δz – δΔE/ΔEσz
σE Δz
ΔE2 ~ V(cosφs+(φs-π/2)sinφs)δΔE/ΔE = ½[δV/V+δφs/(tanφs +1/(φs-π/2))]δφs=- δV/V tanφs
δΔE/ΔE = ½δV/V[1-1/(1+1/(tanφs(φs-π/2)))]δV/V = -1%, φs=66o => δΔE/ΔE = -8.5%
Image from H. Damerau, PhD Thesis, 2005
φs=73o
Δφ ~ (φs-π/2)δΔφ/Δφ = δφs/(φs-π/2)δφs= -δV/V tanφs
δΔφ/Δφ = -δV/V tanφs/(φs-π/2)δV/V = -1%, φs=66o => δΔz/Δz=δΔφ/Δφ = -5.4%δσz /σz = δΔz/Δz – δΔE/ΔE = -5.4% + 8.5% = 3.1% (peak-to-peak)
ΔE
Proposal for conceptual design at 2 GHz based on the ARES-type cavities
1. Fix the value of acceptable bunch length increase from first to the last bunch to δσz /σz = 3%
2. This defines allowed voltage reduction δV/V = -1%, which corresponds to dφb= dV/V (1/tanφs- tanφs) = 1.5o, φs = 66o
3. To assure this voltage reduction the total normalized shunt impedance:
ρ = -dV/V *V2/(PbTb(1-ntrainsTbfrev) ω) = 25 Ω
Parameters of the proposed rf system at 2 GHz
Q-factor ~190000
Total stored energy: W [J] 34
Wall loss per cavity: Pg [MW] 0.11
Number of cavities N=Wω/QPg 20
Normalized shunt impedance per cavity (circuit): ρg =ρ/N[Ω]
1.25
Gap voltage: Vg = sqrt(Wω2ρg/N)[MV] 0.23
Wall loss total [MW] 2.2
Average beam power [MW] 0.6
Total length of the rf system [m] ~40
Bunch phase spread: dφb [o] 1.5
Relative rf frequency mismatch: df/fRequired for compensation dφb
-1.4e-5
Corresponding mean radius position increase: dR=R*df/f [mm]
~0.7
RF station layout ARES type cavities
beam
Reflections from the cavities go to the load
Load
HVPS
18 kV AC
Klystron0.3 MW
Voltage program input
Storage cavity
Circulator
Storage cavity
Superconducting RF optionMaking ARES-type cavity superconducting is probably possible but certainly
beyond the present state-of-the-art in SC RF technologyElliptical cavity is an option but it has relatively high normalized shunt
impedance. Let’s consider TESLA-like cell:
Frequency: f[GHz] 1.3 1 2
Normalized shunt impedance (circuit): ρg=Rg/Q [Ω] (const)
58 58 58
Unloaded Q-factor: Q (~ 1/f2) 5e9 8e9 2e9
Aperture radius: r [mm] (~ 1/f) 35 46 23
Max. gradient in CW: G [MV/m] Scaled to keep gradient constant
14 14 14
Max. gap voltage: Vg [MV] 1.6 2 1
Stored energy per gap: Vg2/2ρgω [J] 2.7 5.5 0.7
gap
Image and pars from PhysRevSTAB.3.092001 Parameters of SC rf system at 2 GHz
Total stored energy [J] 34
Gap stored energy: [J] 0.7
Number of gaps 50
Gap voltage: Vg [MV] 0.09
Normalized shunt impedance per gap (circuit): ρg [Ω]
0.5
Q-factor at 2K 2e9
Wall loss total [W] at 2K 212
Total cryogenic power [MW] at 300K ~0.2
Average beam power [MW] 0.6
Total length of the rf system [m]Dependent on the # of cells per cavity
~10 for 5 cells per cavity
RF station layout for SC cavities
beam
Reflections from the cavities go to the load
Load
PS
18 kV AC
Klystron or IOT
60 kW
Voltage program input
Circulator
Low stored energy option
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
Scaling of NLC DR RF cavity
NLC DR RF cavity parameters CLIC DR RF
Frequency: f[GHz] 0.714 2 1
Shunt impedance: Rg [MΩ] (~ 1/√f)
3 1.8 2.5
Unloaded Q-factor: Q0 (~ 1/√f)
25500 15400
21500
Aperture radius: r [mm] (~ 1/f)
31 11 22
Max. Gap voltage: Vg [MV] (~ 1/f3/4)
0.5 0.23 0.39
Wall loss per cavity: Vg2/2Rg [MW] 0.042 0.015 0.03
HOM (σz=3.3mm)
Total loss factor: kl [V/pC] (~ f)
1.7 4.76 2.38
Fundamental loss factor: k0l
[V/pC] (~ f) 0.26 0.72 0.36
HOM loss factor: k||l [V/pC]
(~ f) 1.1 3.08 1.54
Transverse HOM kick factor: kTt
[V/pC/m] (~ f2) 39.4 309 77.3
From PAC 2001, ChicagoAN RF CAVITY FOR THE NLC DAMPING RINGSR.A. Rimmer, et al., LBNL, Berkeley, CA 94720, USA
From PAC 1995,Collective effects in the NLC DR designsT. Raubenheimer, et al.,
Scaling of the gap voltage is done to keep heat load per meter constant: P/g = Vg
2/2Rgg = Vg2/2ρgQ g => Vg
~1/f3/4
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
Cavity parameters
Number of cavities: N = Vrf/Vg = 4.6/0.23 = 20 = 10 x 2-cells cavities
Gap voltage: Vg = Vrf/N = 4.6/20 = 0.23 MV
Total wall losses [MW] : P0 = Vrf2/2NR = 4.62/(2*20*1.8) = 0.29 MW
Peak beam SR power [MW]: Pb = U0*Ib = 4.2*1.3 = 5.46 MW
Matching condition: Total power lost in the cavities when the beam is in: Pin = Pb + P0 = 5.75 MW
Cavity coupling: β = Q0/Qext = Pin/P0 = (Pb+P0)/P0 = 20
External Q-factor: Qext = Q0/β = 15400/20 = 770
Filling time: tf = Ql/f = Qext/(1+1/β)/f = 770/(1+1/20)/2 GHz = 367 ns
Klystron bandwidth: ∂f ∂f >> 1/tf = 1 / 367 = 2.7 MHz.
AND ∂f >> 1/tgap = 1 / (1402-156) = 0.8 MHz; where tgap – time between the bunch trains
RF system total active length: 10 x 1 m = 10 m
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
Transient beam loading compensation
Transient beam loading compensation with infinite bandwidth klystron
Amplitude modulation from 1 to 0.55 is necessary (see Vin)
Transient beam loading compensation with 0.5% (10 MHz) bandwidth klystron
Amplitude modulation from 1 to 0.35 is necessary (see Vin)
0 1000 2000 3000 4000 5000 6000 7000 8000 90000
0.2
0.4
0.6
0.8
1
1.2
1.4
rev
/2
V/V
in; /
Ib
Vin
Vout
Vrf
Vb
0 1000 2000 3000 4000 5000 6000 7000 8000 90000
0.2
0.4
0.6
0.8
1
1.2
1.4
rev
/2
V/V
in; /
Ib
Vin
Vout
Vrf
Vb
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
Reflections from the cavities go to the load
Basic layout of 2 GHz rf station
2-cells cavity
beam
Load
HVPS
18 kV AC
80 kV DCKlystro
n0.6
MW
Circulator
Voltage program input
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
beam
Reflections from the cavities go to the load
Alternative layout for 2 GHz rf station DR
4-cell cavity
Load
HVPS
18 kV AC
80 kV DCKlystro
n0.6
MW
Voltage program input
Pulse
Compressor
Alternative layout doubles peak power for a pulse of ~600 ns
0 2000 4000 6000 8000 10000 12000 14000 16000 180000
0.5
1
1.5
2
2.5
3
rev
/2
V/V
in; /
V
in
Vout
Circulator
C L I CC L I C
26 Nov. 2010Alexej Grudiev, CLIC DR RF system at 2 GHz.
Summary table for “a la linac”-type
Overall parameters PC-option
Total rf power [MW] >6 >3
Total length [m] 10 5
Number of HVPS 10 5
Number of klystrons 10 5
High voltage power supply (HVPS)
Output voltage [kV] 60
Output current [A] 20
Voltage stability [%] 0.1
Klystron
Output power [kW] 600
Efficiency [%] 50
Bandwidth [MHz] >10
Gain [dB] ~40
C L I CC L I C
9 March. 2010Alexej Grudiev, CLIC DR RF.
Klystron bandwidth
NLC DR RF system:http://www-project.slac.stanford.edu/lc/local/Reviews/cd1%20nov98/RF%20HighPwr_Schwarz.pdfKlystron• High power CW klystrons of 1 MW output power and -3 MHz 1 dB bandwidth at 700 MHz were
developed by industry for APT.• New requirement for Damping Ring klystron is order of magnitude wider bandwidth: 65 nano-seconds
gap in between bunch trains cause variations in accelerating field level during bunch train, resulting in bunch extraction phase variation. This effect can be counteracted by a fast direct feedback loop with about 30 MHz bandwidth.
• A klystron bandwidth of 20 - 30 MHz is within technical know-how for a 1 MW hiqh power klvstron but will result in lower efficiency.
Klystron Dept. Microwave Engineering, H. Schwarz, 1998
http://ieeexplore.ieee.org/stamp/stamp.jsp?arnumber=01476034
A BROADBAND 500 KW CW KLYSTRON AT S-BAND, Robert H. Giebeler and Jerry Nishida, Varian Associates, Palo Alto, Calif. 1969klystron amplifier designed for installation ‘on the 210 foot steerable antenna. This paper will describe the development of a 500 kilowatt CW S-band at the JPL/NASA deep space instrumentation facility a€ Goldstone, California. This tube is an improved version of the 450 kilowatt unit developed in 1967. Its features include 1-1/2 percent instantaneous bandwidth, 58 dB nominal gain and 53 percent nominal efficiency.
• Few percent bandwidth is feasible for 0.5 MW CW klystron• Most critical issue is to determine peak power versus
bandwidth requirements for the low stored energy option.
C L I CC L I C
9 July 2010Alexej Grudiev, CLIC DR RF for CDR.
Impedance estimate in DR, PDR
Calculated RF cavity parameters HOM NLC DR CLIC DR CLIC PDR
Frequency: f[GHz] 0.714 1 2 1 2
Number of cavities: N = Vrf/Vg 2 (3) 16 20 40 48
Total HOM loss factor: k||l * N [V/pC] 2.2 24.6 61.6 61.6 148
Long. HOM energy loss per turn per bunch [μJ]: ΔU = k||
l * N * eNe2
2.8 10 25 32 77
Incoherent long. HOM loss power [kW]: P||
incoh= ΔU * Nbf/h2 2.2 5.6 7.7 19
Coherent long. HOM loss power [kW]: P||
coh~ P||incoh*QHOM *f/fHOM
(if the mode frequency fHOM is a harmonic of 2 GHz)
Careful Design of HOM damping is needed
Total HOM kick factor: kTt * N [V/pC/m] 78.8 1240 6160 3100
14800
Tran. HOM energy loss per turn per bunch [μJ]: ΔU = kT
t * 2πf/c * N * eNe2 * d2
(d – orbit deviation , 10mm assumed)
0.15 1.1 10.5 3.3 32
Tran. HOM loss power is not an issue: < [kW]
Summary tableLow W High W: ARES High W: SC
Train length [ns] 156 312 156 312 156 312
Total stored energy [J] 0.3 34 68 34 68
Shunt impedance (circuit) [MΩ] 36 4.8 2.4 50000 25000
Total rf power [MW] >6 3 6 0.6 1.2
Total length [m] ~10 ~40 ~40 ~10 ~20
Klystron bandwidth [%] > 1 < 0.1 < 0.1
Voltage modulation Strong:Phase + amplitude
No, or very small phase
Could be stronger
No, or very small phase
Could be stronger
Strong HOM damping demonstrated demonstrated demonstrated in single cell
Transverse impedance Highest Lower Lowest
Cryogenic power [MW] 0 0 ~0.2
Main Challenge Voltage modulation for transient
compensation,Low efficiency
Low efficiency Big size
Low R/Q,Rf design both for
fundamental and for HOM
All 3 options seems to be feasible but have different issues summarized below
φs reduction helps a lot here